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936 IEEE TRANSACTIONS ON CIRCUITS AND SYSTEMSII: EXPRESS BRIEFS, VOL. 53, NO. 9, SEPTEMBER 2006
A New Approach for the Design of WidebandDigital Integrator and Differentiator
Nam Quoc Ngo, Member, IEEE
AbstractThis brief presents a general theory of theNewtonCotes digital integrators which is derived by applyingthe -transform technique to the closed-form NewtonCotes inte-gration formula. Based on this developed theory, a new widebandthird-order trapezoidal digital integrator is found to be a class oftrapezoidal digital integrators. The novel wideband third-ordertrapezoidal integrator accurately approximates the ideal inte-grator over the whole Nyquist frequency range and comparesfavourably with existing integrators. Based on the designed wide-band third-order trapezoidal integrator, a new wideband digitaldifferentiator is designed, which approximates the ideal differen-tiator reasonably well over the whole Nyquist frequency range andcompares favourably with existing differentiators. The low orders
and high accuracies of the novel wideband trapezoidal integratorand the new wideband differentiator make them attractive forreal-time applications.
Index TermsDigital differentiator, digital filter, digitalintegrator.
I. INTRODUCTION
DIGITAL integrators and differentiators form an integral
part of many physical systems. Therefore, the design of
sufficient wideband integrators and differentiators is of consid-
erable interest. The frequency response of an ideal integrator is
given by
(1)
and the frequency response of an ideal differentiator is given by
(2)
where and is the angular frequency in radians. Dig-
ital integrators and differentiators are normally designed based
on the definitions given in (1) and (2), respectively.
Recursive digital integrators have been designed by per-
forming a simple linear interpolation between the magnitude
responses of the classical rectangular, trapezoidal and Simpson
digital integrators [1][3]. A linear-programming optimizationapproach has also been proposed to design recursive digital
integrators [4]. However, these integrators are not wideband
because their magnitude responses only approximate the mag-
nitude response of the ideal integrator up to a fraction of the
fullband Nyquist frequency range [1][4]. In [1], a first-order
integrator can only approximate the ideal integrator well in the
Manuscript received August 16, 2005; revised February 9, 2006. This paperwas recommended by Associate Editor C.-T. Lin.
The author is with the School of Electrical and Electronic Engi-neering, Nanyang Technological University, Singapore 639798 (e-mail:[email protected]).
Digital Object Identifier 10.1109/TCSII.2006.881806
low and midband frequency ranges. References [3] and [4] have
reported on the design of low-frequency second-order digital
integrators. In this brief, an alternative approach is proposed
for the design of a novel wideband digital integrator.
Nonrecursive or finite-impulse response (FIR) digital differ-
entiators with linear phase characteristics have been designed
using various techniques for low-frequency [5][9], midband
frequency [10], high-frequency [11] and wideband [12][14]
operations. The FIR wideband differentiators, however, have a
long filter length or high filter order [12][14]. In this brief, a
new wideband recursive digital differentiator with a low filter
order is proposed.In this brief, we present a general transfer function of the
NewtonCotes digital integrators, which is obtained by per-
forming the -transform on the closed-form NewtonCotes
integration formula. From this theory, we find a class of trape-
zoidal digital integrators, in which a third-order trapezoidal
digital integrator is found to have its magnitude response
closely match the magnitude response of the ideal integrator
over the entire Nyquist frequency range. Using the designed
wideband third-order trapezoidal integrator, a new wideband
digital differentiator is designed, which approximates the ideal
differentiator reasonably well over the entire Nyquist frequency
range. The proposed integrator and differentiator comparefavourably with the existing integrators and differentiators, re-
spectively. The brief is organized as follows. Section II presents
a general theory of the NewtonCotes digital integrators, the
design of the proposed integrator and performance compar-
isons of the proposed integrator with the existing integrators.
Section III describes the design of the proposed differentiator
and performance comparisons of the proposed differentiator
with the existing differentiators. The conclusion is given in
Section IV. Note that (the sampling period of the filter)
is used in the frequency plots and the Nyquist frequency is
radians.
II. PROPOSED INTEGRATOR AND COMPARISON
WITH EXISTING INTEGRATORS
A general transfer function of the th-order NewtonCotes
digital integrator is shown in the Appendix to be given by
(3)
where is the feedback delay and is the
-transform parameter. The th coefficient in (3) is given by
(4a)
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NGO: A NEW APPROACH FOR THE DESIGN OF WIDEBAND DIGITAL INTEGRATOR AND DIFFERENTIATOR 937
where the binomial coefficient is defined as
(4b)
The th difference equation in (3) is given by
(5)
When (3) (4)(5) are solved for certain values of and , (3)will take the form of
(6)
where is a real-valued coefficient of the feedforward section.
For example, (where ), (where
), (where ) and (where
) are, respectively, the well-known transfer functions
of the trapezoidal, Simpsons 1/3 (or Simpson), Simpsons 3/8
and Booles integrators, and these integrators have poor approx-
imation of the ideal integrator [1][4], [16]. By solving (3)(4)(5)
for and , the transfer function of a new third-ordertrapezoidal digital integrator is givenby (7), shown at the bottom
of the page, which can be shown to be in the form of(6). By per-
forming a linear interpolation between the magnitude response
of the rectangular integrator and the magnitude response of the
trapezoidal integrator, Al-Alaoui has proposed a first-order dig-
ital integrator which is described by [1], [2]
(8)
Similarly, by performing a linear interpolation between the mag-
nitude response of the Simpson integrator and the magnitude re-
sponse of the trapezoidal integrator, Al-Alaoui has proposed aclass of second-order integrators which is described by [3]
(9)
where . Here we use because it gives a good
magnitude response as described below. Using a linear-pro-
gramming optimization technique, Papamarkos and Chamzas
have designed a class of second-order digital integrators which
is described by [4]
(10)
Fig. 1 shows the magnitude responses of the ideal in-
tegrator, the proposed third-order trapezoidal integrator,
, the Al-Alaouis first-order integrator, , the
Al-Alaouis second-order integrator, , and the Papa-
markosChamzass integrator, . It can be seen that the
Fig. 1. Magnitude responses of the ideal integrator, the proposed third-ordertrapezoidal integrator
H ( z )
, Al-Alaouis first-order integrator H ( z ) ,Al-Alaouis second-order integrator H ( z ) , and the PapamarkosChamzassintegrator
H ( z )
.
Fig. 2. Absolute values of the percent relative errors of the magnitude re-sponses of the proposed third-order trapezoidal integrator
H ( z )
, Al-Alaouisfirst-order integrator H ( z ) , Al-Alaouis second-order integrator H ( z ) ,and the PapamarkosChamzass integrator H ( z ) .
proposed approximates the ideal integrator reasonably
well (to within 6.5% error, see Fig. 2) over the whole Nyquist
frequency range and may thus be regarded as a wideband
integrator.
(7)
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938 IEEE TRANSACTIONS ON CIRCUITS AND SYSTEMSII: EXPRESS BRIEFS, VOL. 53, NO. 9, SEPTEMBER 2006
The absolute values of the percent relative errors of the mag-
nitude responses of the integrators shown in Fig. 1 are shown in
Fig. 2. From Fig. 2, the proposed performs better than
over the whole Nyquist frequency range of
radian. Also, the proposed only performs better than
for radian and radian. In addi-
tion, the proposed only performs better thanfor radian and radian. The phases of
and are exactly over the whole Nyquist frequency
range. The maximum deviations of the phase responses of the
proposed and from the ideal linear phase re-
sponse are (which occurs at radian) and
(which occurs at radian), respectively. Note that the
low order and high accuracy of the proposed makes it
attractive for real-time applications.
III. PROPOSED DIFFERENTIATOR AND COMPARISON
WITH EXISTING DIFFERENTIATORS
Using the approach described in [17], we here describe the de-sign of a new type of recursive digital differentiator by inverting
the transfer function (see (7)) of the wideband third-order trape-
zoidal digital integrator. In taking the inverse of (7), an unstable
pole that lies outside the unit circle at is ob-
tained. Replacing this unstable pole at by in-
verting it to give a stable pole at and multi-
plying the denominator by a factor of to compensate for
the amplitude, the resulting transfer function of the new design
of a third-order recursive digital differentiator is given by (11),
shown at the bottom of the page.
The transfer function of a rectangular-trapezoidal
first-order differentiator proposed by Al-Alaoui is given
by [1]
(12)
Fig. 3 shows the magnitude responses of the ideal differen-
tiator, the proposed differentiator, , and the Al-Alaouis
differentiator, , and the absolute values of the rel-
ative percent errors of the magnitude responses of these dif-
ferentiators are shown in Fig. 4. It can be seen that the pro-
posed differentiator approximates the ideal differentiator rea-
sonably well (to within 5% error, see Fig. 4) over the entire
Nyquist frequency range and may thus be regarded as a wide-
band differentiator. The proposed differentiator almost outper-
forms the Al-Alaouis differentiator in the high-frequency range
of radian, while the Al-Alaouis differentiator outper-
forms the proposed differentiator for radian. It is noted
that the proposed differentiator also outperforms the following
Al-Alaouis second-order differentiators which are the Tick
differentiator [17], the Simpson differentiator [18] and the
Fig. 3. Magnitude responses of the ideal differentiator, the proposed differen-tiator H ( z ) , and Al-Alaouis differentiator H ( z ) .
Fig. 4. Absolute values of the percent relative errors of the magnitude re-sponses of the proposed differentiator H ( z ) and Al-Alaouis differentiatorH ( z )
.
Simpson-trapezoidal differentiator [3] because these differen-
tiators are low-pass differentiators which can only approximate
the ideal differentiator up to radian. In addition,
the new wideband differentiator outperforms the two-point dif-
ference differentiator and the three-point central difference dif-
ferentiator [5]. The new wideband differentiator also compares
favourably with the 10-point low-pass differentiator reported by
Oppenheim and Schafer which has anerror of 12% for a range
of 0.8 of the Nyquist frequency range [6]. The maximum de-
viations of the phase responses of the proposed differentiator
and the Al-Alaouis differentiator from the ideal linear phase
response are (which occurs at radian) and
(which occurs at radian), respectively. Note that the
(11)
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NGO: A NEW APPROACH FOR THE DESIGN OF WIDEBAND DIGITAL INTEGRATOR AND DIFFERENTIATOR 939
low order and high accuracy of the new wideband differentiator
makes it attractive for real-time applications.
IV. CONCLUSION
We have presented a general theory of the NewtonCotes
digital integrators which has been derived by performing the
-transform on the closed-form NewtonCotes integration for-
mula. Using the developed theory, a new third-order trapezoidal
digital integrator has been found to be a class of the trapezoidal
digital integrators. The novel wideband third-order trapezoidal
integrator accurately approximates the ideal integrator over the
entire Nyquist frequency range and compares favourably with
the existing integrators. Using the new design of the wideband
third-order trapezoidal integrator, a new wideband digital differ-
entiator has been designed. The novel wideband digital differen-
tiator approximates the ideal differentiator reasonably well over
the whole Nyquist frequency range and compares favourably
with the existing differentiators.
APPENDIX
DERIVATION OF A GENERAL THEORY OF THE
NEWTONCOTES DIGITAL INTEGRATORS
1) Definition of Numerical Integration: Assume that a con-
tinuous-time signal is given and that its integral
(A1)
is to be determined from a sequence of samples of at thediscrete time where and
is the period between successive samples. Thus, (A1)
can be written as
(A2)
in which the integration interval is divided into a number
of equal segments with each segment having a step size of .
The underlying principle of the numerical integration algorithm
is shown in Fig. 5.
From Fig. 5, (A2) can be divided into two integrals
(A3)
where represents the area of the hatched region ofFig. 5. The
-transform of (A3) is given by
(A4)
where is the -transform of and
is the -transform of . In (A4), is the
-transform parameter, where is the angular fre-
quency, and is the sampling period of the integrator. in(A4) will be determined in the Appendix part 4.
Fig. 5. Graphical illustration of the numerical integration technique.
2) Newtons Interpolating Polynomial: The discrete-time
variables in Fig. 5 are re-defined as and ,
where and . Using these definitions,
in (A3) becomes
(A5)
For the integration interval in (A5), the curve
can be approximated by the th-order Newtons interpolating
polynomial, which passes through data points, as [15]
(A6)
where
(A7)
and
(A8)
(A6) can be further simplified by defining a new quantity
(A9)
which is substituted into (A7) to give
(A10)
Substituting (A10) into (A6) results in
(A11)
3) General Form of the NewtonCotes Closed Integration
Formula: Substituting (A11) into (A5) results in
(A12)
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940 IEEE TRANSACTIONS ON CIRCUITS AND SYSTEMSII: EXPRESS BRIEFS, VOL. 53, NO. 9, SEPTEMBER 2006
From (A7) and (A9), and the limits of integration in
(A12) are changed from to and from to
. Substituting these parameters into (A12) results in
(A13)
where
(A14)
Using , (A8) can be further simplified to
(A15)
(A13)(A14)(A15) describe the general form of the
NewtonCotes closed integration formula.
4) General Theory of the NewtonCotes Digital Integrators:
Taking the -transform of(A13) results in
(A16)
where is the -transform of (A15), which is given by
(A17)
where is the -transform of . Equation (A17)
can be recognized as
(A18)
where
(A19)
Substituting (A18) into (A16) gives
(A20)
Substituting (A20) into (A4), the th-order transfer function,
, of the NewtonCotes digital integrator
can be generally described by (3).
ACKNOWLEDGMENT
The author is thankful to the reviewers for their constructive
criticisms of the work and useful suggestions for improving the
manuscript.
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