advances of composite right/left handed sfmi...
TRANSCRIPT
Advances of Composite Right/Left Handed
S f Mi A li iStructures for Microwave Applications
Tatsuo Itoh
Electrical Engineering DepartmentUniversity of California, Los Angeles
Microwave Electronics Lab
INTRODUCTION
1. Left-Handed (LH) Metamaterials andTransmission Line ApproachTransmission Line Approach
2. Composite Right / Left-Handed (CRLH)Metamaterials
3. Passive Component Applications4. Antenna Applications5. Dielectric Resonator Based CRLH6. SIW based LHM7. Conclusions
Microwave Electronics Lab
1. Left-Handed (LH) Metamaterialsand Transmission Line Approach
Microwave Electronics Lab
Different Approaches of LH MetamaterialsHistorical MilestonesHistorical Milestones
• 1968 : theoretical analysis of hypothetical LH materials by Veselago• 1996/9 : introduction of electric (ε<0) / magnetic (μ<0) plasmon by Pendry• 2000 : experimental demonstration of LH structure by Smith
LH definition: → materials with→ unit-cell << λ effective / macroscopic / homogeneous
0 and 0 0 and || p gn v vε μ< < ⇒ < −
R S A h T i i i A h
UCSD, 2D-LH ( )CjZ ′=′ ω1
Resonant Structure Approach Transmission Line Approach
high-pass( )LjY ′=′ ω1
h i l / i l i h T i i li l i
“BACKWARD WAVES”(e.g. Brillouin, Pierce)
• approach: no simple/rigorous analysis& no design method
• structures: RESONANTlossy & narrow bandwidth
• approach: Transmission line analysis& circuit design methods
• structures: NON-RESONANTlow loss & broad bandwidth
Microwave Electronics Lab
& highly dispersive & moderate dispersion
- L. Brillouin, “Wave Propagation in Periodic Structures”, Mc Graw Hill, 1946- J. R. Pierce, “Traveling-Wave Tubes”, D. Van Nostrand Company, 1950
Anti-parallel Phase / Group Velocities
an0 0dε μ< <• Definition of LHMs: ||p gv v=−or
0 0
,
,
Maxwell:
Plane Wave:
E j B H j Djk r jk rE E e H H e
ω ω∗ ∇× =− ∇× =− ⋅ − ⋅∗ = =
(dir. )k vϕ
0 0
, ,Then, the triad becomesE H k⎛ ⎞⎜ ⎟⎜ ⎟⎝ ⎠
∗ H(dir. )grS v(RH)
, if 0 (RH),
, if ,0 (LH)
HB
Hk E
ω μ μω
ω μ μ
⎧⎪⎪⎪⎨⎪⎪
+ >= =
− <× E
(dir. )S v, if ,
, i
0 (LH
f 0 ( H)
)
,
H
E RDk H
ω μ
ω ε εω
μ⎪⎪⎩
− >= =
<
−×⎧⎪⎪⎪⎨ E
H( )gr
(LH)
, iEk ω
ω ε+
Poynting Vec
0 (L
tor: ( )
)
Hf .
S E H RH
ε⎨⎪⎪⎪⎩
∗ ∗= ×
< E(dir. )k vϕ
Microwave Electronics Lab
y g ( )
General Classifications of Material Based on (ε,μ)
conventionalplasma
μplasma
wire structure (RH)
air air
0, 0n εμε μ> >
=+0, 0ε μ< >
εNo transmission
split rings structureferrites
LHMs
0, 0ε μ< <
ε(Permittivity)
split rings structure
0 0ε μ> <
0, 0ε μair air
0, 0ε μ> <No transmissionn εμ=−
Microwave Electronics Lab
Distributed Model of Transmission Line LH structure
kL∆z
v >0 v >0
β
C∆zvp>0, vg>0
β∆z→0
kC/∆z
L/∆zvp>0, vg<0
β∆z→0
Microwave Electronics Lab
β∆z→0
LH TL Material Constitutive Parameters
′M i M ll t ′Zj
μω′
=• Mapping Maxwell toTelegrapher’s eqs :
Yj
εω′
=
• LH TL parameters: ( )1Y j Lω′ ′=( )1Z j Cω′ ′=lossless
j Z Yγ β ′ ′= =L′C ′ [ ]F m⋅
• Dispersive ε & μ:t
( )21 0 !Cμ ω ′= − < ( )21 0 !Lε ω ′= − <
jγ β[ ]H m⋅
non-resonant( )
• Dispersive n:
( )
0 0 0 0 !c c cZ Yn ε μ β′ ′
<• Dispersive n:
( ) 1 0ωε⎧∂
⎪
0 0 02
0 !r rnj L C
ε μ βω ω ω
= = = = − <′ ′
• EntropyConditions:
( ) ( )( )
( )2 2
00
1 0
LW E Hωε ωμ ωω ω ωμ
= >⎪⎫∂ ∂ ⎪ ′∂= + > ⇒⎬ ⎨∂ ∂ ∂⎭ ⎪ = >⎪⎩Microwave Electronics Lab
0Cω
>⎪ ′∂⎩
Realization of 1D LH TLsLumped Element Implementationp p
Ideal Elements Chip Components
Distributed Implementation (Microstrip)
microstrip series shunt
Interdigital C & spiral / stub L Interdigital C & stub Lp
line interdigitalcapacitor
spiralinductor
T-junctionunit cell
shortedshorted
via toground
MIM-C
shortedstub
MIM-C
shortedstub
interdigitalcapacitors
h d b
GPGPMultilayer → LTCC
Microwave Electronics Lab
shorted stubinductors
Realization of 2D Metamaterials2D Lumped Element Structure: Meta-Circuit (“closed”)2D Lumped Element Structure: Meta-Circuit ( closed ) RH
2RL
LH
2 LC
2D interconnection Chip Implementation
yzRC2RL
2RL
2RL
LL
L
2 LC
2 LC2 LC
yz yy
x
y
x
y
x
2.5D Textured Structure: Meta-Surface (“open”) Enhanced Mushroom Structure Uniplanar Interdigital Structure
top patch
capspost
top patch
ground plane
post
Unit cell
sub-patches
ground plane
via
Microwave Electronics Lab
2. Composite Right / Left-Handed (CRLH)Metamaterials
Microwave Electronics Lab
Ideal Composite Right / Left-Handed (CRLH) TL
0, ZβRL′ LC′ [ ]F m⋅
Infinitesimal Circuit Model Transmission Line Representation
RC′ LL′[ ]H m
[ ]F m[ ]H m⋅
d[ ]F m
0zΔ →
, wherej Z Yγ β ′ ′= =
Balanced CasePropagation Constant
Definition: R L L RL C L C L C′ ′ ′ ′ ′ ′= =
1 1,R RL L
Z j L Y j Cj C j L
ω ωω ω
′ ′ ′ ′= + = +′ ′
⇓
22
1 2R RL CL C
β ωω
′ ′= + −′ ′
↓
( ) 22
1 R RR R
L Cs L CL C L C
β ω ωω
⇓
⎛ ⎞′ ′′ ′= + − +⎜ ⎟′ ′ ′ ′⎝ ⎠
1L L
R RL L
L C
L CL C
ω
ωω
′ ′= −′ ′
RL′
RC′LL′
LC′
Microwave Electronics Lab
L L L LL C L Cω ⎝ ⎠RH LHβ β= +
( ) 1 21 1 1 11 if min , and 1 if max ,R L L R R L L R
sL C L C L C L C
ω ω ω ω ωΓ Γ
⎛ ⎞ ⎛ ⎞= − < = + > =⎜ ⎟ ⎜ ⎟⎜ ⎟ ⎜ ⎟
⎝ ⎠ ⎝ ⎠
Phase/Group Velocities: No Physical Law ViolationPure LH TL Balanced CRLH TL Unbalanced CRLH TLPure LH TL
LC ′
Balanced CRLH TL Unbalanced CRLH TL
RL′ LC′
[ ]H m
[ ]F m⋅RL′ LC′
[ ]F m⋅[ ]H m
LL ′
0zΔ →
RC′ LL′[ ]F m
[ ]H m⋅
0zΔ →
RC′LL′ [ ]H m⋅
[ ]
[ ]F m
0zΔ →
2
1L C
βω
= −′ ′
0zΔ →
22
1LC
CL
ωβω
= −′
′′
′ 22 1
L L L L
R RR R L C L C
L CL Cω
ωβ⎛ ⎞
= + −′
′ ′′ ′
′+
′⎜⎝ ′ ⎟
⎠10 2 0 2 0
balanced: R L L RL C L C L C′ ′ ′ ′ ′ ′= =
CLω
2468
10
0.51.01.52.0
0.51.01.52.0
-8-6-4-20
vp/(nc0) vg/(nc0)
-1.5-1.0-0.50.0
vp/(nc0) vg/(nc0)
-1.5-1.0-0.50.0
vp/(nc0) vg/(nc0)
GAP0gnv c0pnv c
0gnv c0pnv c
0gnv c0pnv c
( ) : not physical!gv ω → ∞ = ∞( ) 0gv c nω → ∞ =
( ) ( )2( ) 0gv c nω → ∞ =
-10 ω -2.0ω
-2.0ω0ω 1ωΓ 2ωΓ
Microwave Electronics Lab
( )g ( ) ( )0 0 2gv c nω ω→ =( )g
Dispersion Diagram and Group Velocity (CRLH)
⎧ ⎫⎛ ⎞⎪ ⎪( )2 sina aβ
1
( ) 22
1 1cos 12
R RR R
L L L L
L Ca L CL C L C
β ωω
⎧ ⎫⎛ ⎞⎪ ⎪= − + − +⎨ ⎬⎜ ⎟⎪ ⎪⎝ ⎠⎩ ⎭
( )
3
sin1g
R RL L
a av
L CL C
β
ωω
= −⎛ ⎞
−⎜ ⎟⎝ ⎠
1 21 1: ,R L L RL C L C
ω ωΓ ΓΓ = =1
2 22 2 2 2 22 2 2 21 01 02 01 02R R 01 022
2
: 2 22 2
X
X
Xω ω ω ω ωω ω ω ωω
⎧ ⎫⎫ ⎛ ⎞+ +⎪ ⎪= + + −⎬ ⎨ ⎬⎜ ⎟⎝ ⎠⎭ ⎪ ⎪⎩ ⎭
∓
1balanced: 1 0 !2R L L R g
R R
L C L C va L CΓ= → = ≠unbalanced: 0R L L R gL C L C v Γ≠ → =
ω ωmatching
2Xω 2XωRH/RH/
0R L
R L
L LZC C
= =
2ωΓ
2XωRH/+zRH/ z−
1 2 0ω ω ωΓ Γ= =
RH/+zRH/ z−
0aλ Γ
⎤ =⎥⎦homogeneous
,β α
1ωΓ
aπ+aπ− 0
1XωGAP
LH/+z LH/ z−,β α
1 2 0Γ Γ
1Xω
aπ+aπ− 0
LH/+z LH/ z−homogeneous
isotropic
Microwave Electronics Lab
aπ+aπ 0Γ XX
aπ+aπ 0Γ XX
Guided Wavelength along a CRLH-TLFull-wave simulations (HFSS)( )
LH RHGAP interdigitalcapacitors
24-cells prototype
2λ π β= = Characteristics
shorted stubinductors
( )2 1R Ra LC
β
π ω ω∝2
2 !L La L C
λ π β
πω ω
=
= ∝
Characteristics• LH / RH range: backward / forward
propagation verified• λg proportional ω in LH range and
1.0 1.35 1.70 2.05 2.20 2.70 3.402.30
g
to 1/ω in RH range verified
ff
Microwave Electronics Lab
0f∼LH ← RH→ fcf
3. Passive Component Applications
Microwave Electronics Lab
Dual-Band Components, E.g.: Quadrature Hybrid( ) ( )31 21 (deg)S Sϕ ϕ ϕΔ = −
CRLH / CRLH hybrid
CRLH1 2270
360
( ) ( )31 21 (deg)S Sϕ ϕ ϕΔ
NB: Conventional quadrature:restricted to odd harmonics
CRLH
CRLH CRLH
34
( )2 1 90nϕ
°
Δ =
− + ⋅ 180
270 because only control on slope
1
Dispersion Engineering:
CRLH 34
0
90
1fCRLH
2f conv2 13f f=
f
DC offset
0f
01
2 R R L L
fL C L Cπ
=
p g g
• dual-band functionality for anarbitrary pair of frequencies f1, f2
0
90−
f
• principle: transition freq. (LH-RH)provides DC offset additional degreeof freedom with respect to the
h l ( ) ( )SS
180−
270− conv. RHphase slope
• BW does not become narrower!
• applications in multi-band systems
( ) ( )2131 SS ϕϕ −360−
CRLH
1L Cϕ ω⎛ ⎞
′ ′Δ = − +⎜ ⎟⎜ ⎟
RH R RL Cϕ ω ′ ′Δ = −
Microwave Electronics Lab
• can be extended to many components LH R RL L
L CL C
ϕ ωω
Δ = +⎜ ⎟⎜ ⎟′ ′⎝ ⎠
Optimal solutionBesides the consideration for minimal length of each
CRLH TL, what else needs to be considered? B d id hBandwidth
The final solution: #4The final solution: #4
Microwave Electronics Lab@ 2.4GHz (f1) @ 5.2GHz (f2)
Experiment
Microwave Electronics Lab
Summary of performance
55% size reduction compared to the conventional rat-race coupler at 2.4GHz
Σ−port Measurement Δ−port Measurement
Microwave Electronics Lab
Broadband Microstrip-to-CPS Transition and its Antenna Application
Microstrip line
CRLH-TL Using unique phase slope and phase control prosperities of CRLH TL. to
+90º0º
0f02 f
03 f
CRLH-TL
control prosperities of CRLH TL. to have broadband out of phase characteristic. (Dispersion Engg)85% back to back transition03 f
-90º
Mi t i
-180º-270º
85% back-to-back transition.65% bandwidth of Quasi-Yagiantenna (~15% enhancement)
Microstrip270
1W3L3Lpower divider
10L 11L4/gλ
1W
1W
2W
2L
3L
4L6L
7L8L
5L
4/gλ
1W
1W
2W3W1L
2L 4L
5L
7L 8LC
CPS
1W6L
1W3W
Lump Elements
1L
via12LLumped
Elements
2 7
1WLC
LL
via
Microwave Electronics Lab
CRLH Transmission line
Microstrip ground
Broadband BSF Measured Results
3dB insertion loss BW : 130% (2GHz~9.6GHz)
10dB signal rejection BW : 78% (3GHz~8GHz)
Next passband at higher frequency end with minimum insertion loss
of -1.7dB @ 9.8GHz
10 2 10
0|S11|
|S21|
d
εr=10.2
h=1.27mm -20
-10
21| (
dB)
|S21|
port 1 port 2d1
d2 -40
-30
S 11|
& |S
2
measurement
lumped element1 2 3 4 5 6 7 8 9 10
-60
-50
|S
simulation
Microwave Electronics Lab
microstrip ground frequency (GHz)
CRLH Harmonic Tuning Approach
90 deg @f0
600
800
))+72
03)
))
+180 deg @f0 -90 deg
CRLH-TL90 deg @f0
600
800
))+72
03)
))
+180 deg @f0 -90 deg
CRLH-TL
0
200
400
hase
(S(2
,1))
p(ph
ase(
S(4
,
-270 deg @3f0
@2f0
0
200
400
hase
(S(2
,1))
p(ph
ase(
S(4
,
-270 deg @3f0
@2f0
+180 deg @f0-90 deg @2f0 2 3 4 5 6 71 8
-200
0
-400unw
rap(
phun
wra
p
+180 deg @f0-90 deg @2f0 2 3 4 5 6 71 8
-200
0
-400unw
rap(
phun
wra
p
-90 deg @2f0-270 deg @3f0
2 3 4 5 6 71 8
freq, GHzRH-TL
-90 deg @2f0-270 deg @3f0
2 3 4 5 6 71 8
freq, GHzRH-TL
• Single CRLH-TL for two harmonics (Dispersion Engineering)
• Reduced number of stubs leads to: Compact circuit size, Reduced associated loss
• Single CRLH-TL for two harmonics (Dispersion Engineering)
• Reduced number of stubs leads to: Compact circuit size, Reduced associated loss
f=2.4 GHz P1dB P.A.E
Class F 24 dBm 63%
lossloss
Microwave Electronics Lab
Class F 24 dBm 63%
ZeroZerothth Order CRLH ResonatorOrder CRLH ResonatorDispersion diagram 7 cell CRLH resonatorspe s o d ag a
ω
ωXωN – 1
7 cell CRLH resonator
ω
ωΓ2
ω0
ω1
ω2
ω3
ω−1ω−2ω 3 2 n = 013
0–1
1 2 3 4 5 6n = 02
0–1
1 2 3 4 5 6n = 02
Resonance characteristicsField distribution
ωc
βk− k 0
ωΓ1ω−3
ω−N +1
π π2π… …
–2 n = 0–1 –3–20
–40
21| (
dB) |S21|
|S11|
6–2–3
–4
–5
–20
–40
21| (
dB) |S21|
|S11|
6–2–3
–4
–5
Resonant modesβ0 = 0 ω0
kc− kc 0Nπ
Nπ2
Nπ
−… …
–60
|S2
80
Survives with increasing loss!!–6
10 Ω1 Ω
R = 0 Ω–60
|S2
80
Survives with increasing loss!!–6
10 Ω1 Ω
R = 0 Ω
10 Ω1 Ω
R = 0 Ω
β±1 = kc / (N – 1)
β0 0
ω1,ω−1
ω2, ω−2
0
β±2 = 2 kc/ (N – 1) • n=0: no dependence on physical size
2 4Frequency (GHz)
1 5–80
32 4Frequency (GHz)
1 5–80
3
…
ωΝ, ω−Νβ±N = kc
supercompact resonator• Initial prototype: more than 2x sizereduction and experimental Q0 = 290 !
Microwave Electronics Lab
N-Port In-Phase Series Divider Based on Infinite Wavelength
2 3 4 5 6
f∞=2.37 GHz1
13 Cells, 5 Output Ports
Experimental ResultsExperimental Results
Microwave Electronics Lab
Power Dividing (APMC 2005)
~P1
-20
-10
Bc]
PN@10 KHz offsetPN@100 KHz offsetPN@1 MHz offset
Single
Phase noise measurement
10.33dBm
0 67
P2 P3 P4
-40
-30
-20
nois
e po
wer
[d
S g eosc.
5 dBm
4.83 dBm
4.83 dBm
0.67 dBm loss
-70
-60
-50
Rel
ativ
e ph
ase
n
-20
Harmonic measurement
1 2 3 4Port number
-80
R
-30
pow
er [d
Bc]
Single osc.
• Equal amplitude
-50
-40
ve h
arm
onic
p • Equal amplitude distribution observed
• Harmonic suppression b d
1 2 3 4-70
-60
Rel
ativ 2nd Harmonic
3rd Harmonic4th Harmonic
observed
• Reduction in phase noise
Microwave Electronics Lab
Port number
Free Space Power Combining Using Metamaterial Coupler
0Endfire antennas
Oscillators Non uniformly spaced power divider
5
0
e [d
B]
osc. arraypassive array
-5
ve a
mpl
itude
-10
Rel
ativ
Osc. locking port
Output Array locking port
-90 -75 -60 -45 -30 -15 0 15 30 45 60 75 90Angle [degrees]
-15
• Spacing is dense and non-uniform
Antenna spacing: 0.18λo (23mm), 0.46 λo (58mm),
• Measured array EIRP= 18 dBm• Measured array EIRP= 18 dBm
• Estimated Posc. = 11.5 dBm based on passive array gain of 6.5 dBi
• Estimated combining efficiency of 78%
Microwave Electronics Lab
Estimated combining efficiency of 78%
N = 2 caseCMOS Application
N-Single-Ended-CRLH-Unit-Cell Ring Resonator
N x βd=2nπ n=0 ‐1 ‐2 … ‐N/2
Dispersion
RFIC 2009 RTU3A 2 A D l B d W CMOS O ill t ith L ft H d d R t
Microwave Electronics Lab
RFIC 2009 RTU3A.2: A Dual Band mm-Wave CMOS Oscillator with Left-Handed Resonator
Chip Micro-PhotographComplete Circuit
W/L=10/0.08um
C 50f
Measurement Summary
Schematic
W/L=16/0 08um
C=50f
L=200p
Process IBM 90-nm Digital CMOS Process
Frequency Band 21 GHz and 55 GHz
Measurement SummaryOutput Spectrum and Phase Noise
/0.08um
Frequency Switching Range (GHz) 34.3 GHz
Frequency Switching Range (%) 62% of highest oscillation frequency
Running at 21 GHz Phase Noise @ 1 MHz offset (dBC/Hz) -100.8
Running at 55 GHz Phase Noise @ 1 MHz offset (dBC/Hz) -86.7
VCO-Core Power (mW) 14
VCO-Core Area 150 µm × 60 µm
Switch On
Oscillation freq: 21.3GHz
Phase Noise -100.8 dBC/Hz
at 1MHz offset
Switch Off
Oscillation freq: 55.6GHz
Phase Noise -86.67 dBC/Hz
at 1MHz offsetRFIC 2009 RTU3A 2 A D l B d W CMOS O ill t ith L ft H d d R t
Microwave Electronics Lab
at 1MHz offset at 1MHz offsetRFIC 2009 RTU3A.2: A Dual Band mm-Wave CMOS Oscillator with Left-Handed Resonator
4. Antenna Applications
4a. Leaky Wave Antennas
Microwave Electronics Lab
Composite Right/Left-Handed MetamaterialsRegion (I):Region (I):
Left-handed Guided mode
0<pgvv
R i (II)
0cωβ −<(II)LH
Radiation
(III)RH
Radiation
β=+ω
C 0
ω
β=-ωC
0
Unbalanced
Dispersion Diagram
0cωβ −>
Region (II):Left-handed
Radiating mode0<pgvv
R i (III)
Radiation Radiation
(I)LH
Guided (IV)ω
ω2ω0
UnbalancedBalanced
Region (III):Right-handed
Radiating mode0>pgvv
R i (IV)0cωβ <
( )RH
Guided
βd
ω1
Region (IV):Right-handed
Guided mode0>pgvv
0cωβ >lC ws
β
lsg
wCLR CL
dvCR LL
Microstrip Model Circuit Model
Microwave Electronics Lab
Backfire-to-Endfire Leaky-Wave AntennaAntenna Configuration CRLH dispersion diagramMain Beam RadiationAntenna Configuration
y
bwd broadside
CRLH dispersion diagramω0cβω −=
IILH
IIIRH
0cβω +=( )rad 0asin kθ β=
Main Beam Radiation
x
ysource
fwd
θ
longitudinalI
LHIVRH
LHRAD.
RHRAD.
0kθ 2 2
0k k β⊥ = −
z
fwdlongitudinalpolarization
β
LHGUIDANCE
RHGUIDANCE
0ωβ0 β⊥
Main beam θ versus ω (meas.)
90
III.
0f0 2c β π maxf0
α / β diagram (meas.)
2 0.120f0 2c β π maxf0 60
90120
Radiation Patterns (meas.)
0
30
60
g A
ngle
(deg
) II.LW-LH
LW-RH
z
I.Guided
-LH
30
60
90-1
0
1 β / k0 α / k0
/ k0
0.06
0.08
0.10
k 0
III. LW-RH
I. Guided
-LH-30
-20
-10
0
30150
180-30
ωω
2 3 4 5 6 7-90
-60
-30
Sca
nnin
g
x y
θ120
150
1802 3 4 5 6 7
-4
-3
-2β /
0.00
0.02
0.04 α /
II.LW-LH
210
240270
300
330
-20
-10
0
3.4 GHz 3.9 GHz 4.3 GHz
Microwave Electronics Lab
Frequency (GHz)2 3 4 5 6 7
Frequency (GHz)270
Electronically Scanned LW Antennaω
( )
( )
0
2
asin
1 1cos 1 R R
k
L Ca L C
θ β
β ω
=
⎫⎧ ⎛ ⎞⎪+ +⎨ ⎬⎜ ⎟
cω β=
ω
( ) 2
0
cos 12
R RR R
L L L L
R L
a L CL C L C
L LZC C
β ωω
= − + − +⎨ ⎬⎜ ⎟⎪⎩ ⎝ ⎠⎭
′ ′= =
′ ′0ω
3VR LC C 3V
2VV
shuntvaractor via Vb (-)
2
0V
β =1
0RHV
β >3
0LHV
β <1V
β
varactor
seriesvaractors
Vb ( )
900 V
0°900 V
0°
Z
−
varactors
Pin
DC feed 5
0
30
60120
150
0 V 5 V 15 V
-30° +30°
-60° +60°5
0
30
60120
150
0 V 5 V 15 V
-30° +30°
-60° +60°
bias
ZLDC feedvia
-10
-5
0180-10 +90°dB-10
-5
0180-10 +90°dB
Microwave Electronics Lab
biaswiresVb (+)
10 01801010 018010
capacitoralinterdigit:A B′
Unit-Cell Implementationcapacitor alinterdigit :A
A B
+
+
BGND
Z Z
L2CL2CRL 2 RL 2
Z Z
A′ B′varactor
stub (via) shorted :BLL RC
Y
var,RL var,LC var,LC var,RL
1,RL 1,LC 1,LC 1,RL
Reverse biasing to VaractorsAnodes of varactors : GND Cathodes of varactors: Biasing
1,LL
var,RC 1,RC 2,LLDCL
DCV
YA′
Cathodes of varactors: BiasingThe cathodes of three varactors in the same direction
Only one bias circuitry in unit cellSeries and Shunt Varactors
Fairly constant characteristic impedance
YGND inductor
Bias Configuration
Fairly constant characteristic impedanceAdditional degree of freedom for wider scanning range
Back to back configuration of two series varactorsFundamental signals : in phase and add upHarmonic signals: out of phase and cancel
Microwave Electronics Lab
Harmonic signals: out of phase and cancel
[1] S. Lim, C. Caloz and T. Itoh, “Electronically-Controlled Metamaterial-Based Transmission Line asa Continuous-Scanning Leaky-Wave Antenna.” IEEE-MTT Int’l Symp., Fort Worth, TX, Jun. 2004.
Beamwidth Control Capability: PrincipleBeamwidth Control Capability: Principle
Beamwidth Beamwidth
U U U U U U U U U U U U1U 2U 3U 4U 5U 6U
0V 0V 0V 0V 0V 0V
1U 2U 3U 4U 5U 6U
1V 2V 3V 4V 5V 6V
Uniform biasing Non-uniform biasing
Uniformly biased periodic TLEach unit cell radiates toward the same angleHigh directivityHigh directivity
Non-Uniformly biased periodic TLEach unit cell radiates toward different angles
Microwave Electronics Lab
Beamwidth is determined by the superposition of each cellBroader beamwidth
Conformal Leaky-Wave Metamaterial Antenna:
C f i ti l l0I0 0I0
ξ 2ξ 3ξ 4ξ 5ξp
d
Co
• Conforming a conventional planar LWA results in radiated beam dispersion and decreased gainnt
iona
l
1θ− 2θ
onformation
dispersion and decreased gain
• CRLH metamaterial unit-cells can conv
en
Section 1
Section 2Section 3
I00
Mo
be adjusted to compensate radiation (beam dispersion)
1θ 2θ−odification
• Implemented static solution for broadside beam (3 sections)fie
d
Modified section 1
Modified section 2
Modified section 3
I00mod
i
Microwave Electronics Lab
Static 3-section conformal prototype implementation:
• Similar concept can be implemented in dynamic fashion with tunable components (varactors, t )etc.)
30°
45°60°
75°90°105°120°
135°
150°
PlanerOrig. ConformMod. Conform 30°
45°60°
75°90°105°120°
135°
150°
PlanerOrig. ConformMod. Conform 30°
45°60°
75°90°105°120°
135°
150°
PlanerOrig. Conform
30°
45°60°
75°90°105°120°
135°
150°
PlanerOrig. Conform
0°
15°
30150
165°
±180° -20-15-10-50
Mod. Conform
0°
15°
30150
165°
±180° -20-15-10-50
Mod. Conform
0°
15°
30°150°
165°
±180° -20-15-10-50
gMod. Conform
0°
15°
30°150°
165°
±180° -20-15-10-50
gMod. Conform• Modified beamwidth due
to 3-section design is narrow, comparable to
-165°
-150°
-135°-120° -60°
-45°
-30°
-15°
GHzf 7.3=
-165°
-150°
-135°-120° -60°
-45°
-30°
-15°
GHzf 7.3=
-165°
-150°
-135°-120° -60°
-45°
-30°
-15°
GHzf 4.3=
-165°
-150°
-135°-120° -60°
-45°
-30°
-15°
GHzf 4.3=
non-conformal antenna
Microwave Electronics Lab
120-105°-90° -75°
60120-105°-90° -75°
60 120-105°-90° -75°
60120-105°-90° -75°
60
Balanced symmetric unit-cell implementation:
p 4Symmetric unit-cell equivalent circuit Unit-cell Dispersion Diagram
l
wRL RCLC
LL
3
cy (G
Hz) Leaky-RH
SwSl
Cl
LL
RCRLLC
2Freq
uenc
Leaky-LH
Common modeDifferential modeAir line
0 40 80 120 160 200Phase constnat (rad/m)
1
Differential mode operation due to symmetric unit-cell Even mode suppression in LH regionBalanced CRLH based leaky wave antenna provides continuous scanningBalanced CRLH-based leaky-wave antenna provides continuous scanning
Microwave Electronics Lab
30-cell differential mode CRLH antenna
Metamaterial-based Antenna System Application:
+ +
- -
Integrated mixer system schematic
Balanced mixer integrated with CRLH differential mode antenna:Differential mode leaky-wave operationEven mode suppression – low LO leakageBalanced CRLH-based leaky-wave antenna provides continuous scanningHigh RF-LO isolation
Microwave Electronics Lab
High RF LO isolation
Measured Results:
IF1 0
B)
Radiated patterns
IF1
LO
-20
-10
tive
Pow
er L
evel
(dB
Integrated system hardware:Mixer board
IF1
-60 -40 -20 0 20 40Angles (degree)
-30
Rel
at
2100MHz2300MHz2400MHz
1.96 GHz – 2.40 GHz operation
-20
-15
(dB)
LO leakage patterns
Measured S-parameters:
p21 dB avg. conversion loss-21o – 0o scanning in LH region
-20
-10
0
(dB
)
Leaky-LH
-10
0
(dB
) -35
-30
-25
elat
ive
Pow
er L
evel
(
-40
-30
S11,
S21
S11_commonS21_common
-30
-20
S11,
S21
S11_differentialS21 differential
Leaky-LH -60 -40 -20 0 20 40Angles (degree)
-45
-40Re 2100MHz
2300MHz2400MHzStop band
characteristic in even mode excitation
Microwave Electronics Lab
1.8 2 2.2 2.4 2.6 2.8 3 3.2 3.4 3.6 3.8 4Frequency (GHz)
-50_
1.8 2 2.2 2.4 2.6 2.8 3 3.2 3.4 3.6 3.8 4Frequency (GHz)
-40_excitation
Distributed Amplifier with CRLH-TL LWA
Conventional DA with FET DA using CRLH and MS TLsConventional DA with FET DA using CRLH and MS TLs
A 5 unit-cell distributed amplifier with MS-TL and
Equivalent circuit of FET
CRLH-TL leaky wave antenna.
Equivalent circuit of CRLH section
Tuned
Microwave Electronics Lab[6] K. Mori and T. Itoh, “Distributed Amplifier with CRLH-Transmission Line Leaky Wave Antenna,”
European Microwave Conference, Amsterdam, October 2008.
Radiation Pattern
inP
0
10
1.8GHz 60
90
[deg
LH
Rad.
RHRad.
0
102.0GHz
0
102.2GHz
0
10
2.4GHz0
10
2 6GHz0
10
0
10
0
103.2GHz
0
10
0
10
-10
0
[dB
i]
-30
0
30
dire
ctio
n
-10
0
[dB
i]
-10
0
[dB
i]
-10
0
[dB
i]
-10
0
[dB
i]
2.6GHz
-10
0
[dB
i] 2.8GHz
-10
0
[dB
i] 3.0GHz
-10
0
[dB
i]
-10
0
[dB
i]
3.4GHz
-10
0
[dB
i]
-20 -90
-60
30
Max
imum
-20-20-20-20-20-20-20-20-20
-90 -45 0 45 90Angle [deg]
1.8GHz
1 2 3 4Frequency[GHz]
M
Maximum direction
-90 -45 0 45 90Angle [deg]
2GHz
-90 -45 0 45 90Angle [deg]
2.2GHz
-90 -45 0 45 90Angle [deg]
2.4GHz
-90 -45 0 45 90Angle [deg]
2.6GHz
-90 -45 0 45 90Angle [deg]
2.8GHz
-90 -45 0 45 90Angle [deg]
3GHz
-90 -45 0 45 90Angle [deg]
3.2GHz
-90 -45 0 45 90Angle [deg]
3.4GHz
-90 -45 0 45 90Angle [deg]
1.8GHz 2GHz 2.2GHz2.4GHz 2.6GHz 2.8GHzLH
Microwave Electronics Lab42
1.8GHz
Measured radiation pattern
Maximum direction2GHz2.2GHz2.4GHz2.6GHz2.8GHz3GHz3.2GHz 3.4GHz2.4GHz 2.6GHz 2.8GHz3GHz 3.2GHz 3.4GHz RH
4. Antenna Applications
4b. Resonant Antennas
Microwave Electronics Lab
Small Antenna – Mushroom Type
topMIM capacitance
RT/Duroid 6010LM
RT/D id 880RT/Duroid 5880
1/14λ x 1/14λ x 1/39λ vias
18.2 mm 18.2 mm
1/14λ0 x 1/14λ0 x 1/39λ0
80.254mm6.32mm
Sub2
Sub1 microstrip ground
Microwave Electronics Lab
Sub1 p g
Small Antenna – Mushroom Type (Exp. Results)
Max gain : 0.6dBi
Highest efficiency:
5 9dB ~ 26 %
0 2
5.9dB 26 %
gain
10
-5
0
s (d
B)
-2
0
ncy
(dB
) gain
-15
-10
etur
n Lo
ss
-6
-4&
Effi
cien
f =1 17GHzefficiency
0.2 0.4 0.6 0.8 1 1.2 1.4 1.6 1.8 2-25
-20Re
1.17 1.1725 1.175 1.1775 1.18 1.1825 1.185-10
-8
Gai
n f-1=1.17GHz
Microwave Electronics Lab
Frequency (GHz) Frequency (GHz)
Compact Dual-Band Antenna (PCS/Bluetooth)
• Based on anisotropic metamaterial.
• Half-wavelength distribution• Half-wavelength distribution.
• 96% size reduction.
x-directionDispersion Diagram
x-direction
y-direction
Microwave Electronics Lab
Compact Dual-Band Antenna (PCS/Bluetooth)
1/17λox1/17λox1/19λo @ 2.37 GHz
~ 96% size reduction
PCS (1.96 GHz) Bluetooth (2.37 GHz)
Gain: -3.0 dBi Gain: -2.3 dBi
Efficiency: 29% Efficiency: 25%
Microwave Electronics Lab
CRLH Infinite Wavelength Patch Antenna
Constant Field Distribution for Monopolar Radiation• Similar to TM01 mode of circular patch antenna.
Monopolar radiation pattern is achieved• Monopolar radiation pattern is achieved.
• Size of patch can be arbitrary.
z
CRLH Square Patch Antenna(infinite wavelength)
z
y MS
x
Microwave Electronics Lab
x
Backward Wave Dual-Mode Antenna (APMC 2005)
f =4 015 GHz f 1 =3.560 GHzf0=4.015 GHzgain=2.3 dBiefficiency=75.0%
f-1 3.560 GHzgain=-2.5 dBiefficiency=22.5%size: λ /5 7 x λ /5 7 x λ /54
0
size: λo/5 x λo/5 x λo/50 size: λo/5.7 x λo/5.7 x λo/54
-10
0
030
60300
330
20
-10
0
030
60300
330
-30
-20
90270-30
-20
-30
-20
90270-30
-20
120
150180
210
240-10
0 Phi=0° Phi=90°
120
150180
210
240-10
0 Phi=0° Phi=90°
Microwave Electronics Lab
Broadband Small Antenna
h1=3.16, h2=0.254, L1=L2=40, D1=4, D2=0.1, D3=14, D4=1.2, D5=1.75. d1=7.8, d2=24, d3=8, h2εr2
εr1=2.2 εr2=10.2
L1
d
d4=18.1, d5=2, d6=12.1, d7=0.2, d8=0.24, h1εr1
d1 d2Unit: mm d3
antenna groundD1
D
D2D5
L2d4
D1d845°
2
y ddmatching groundD2
D2
D5
groundmicrostrip groundx
y d5
d6
d7ground
D3 D4
D5
Microwave Electronics Lab
A Power Amplifier Integrated with a CRLH MM Antenna
Implementation microwave electronics labImplementation
“A power amplifier integrated with a composite right/left-handed metamaterial antenna,” Asia-Pacific Microwave
Microwave Electronics Lab
p p g p g ,Conference 2009, December 7 -10, 2009, Singapore, Paper TU4F-4, (C. M. Schmid, T. Itoh and A. Stelzer).
A Power Amplifier Integrated with a CRLH MM Antenna
Measurements microwave electronics labMeasurements
Gain:Gain:
Simulation: 10 4 dBSimulation: 10.4 dB
Measurement: 10.2 dB
Power added efficiency (PAE):
Simulation: 62 %
Microwave Electronics LabMeasurement: 58 %
5. Dielectric Resonator Based LHM
Microwave Electronics Lab
LHM Structures Using DRs1) Two DR scheme1) Two-DR scheme• Configuration: Combination of TE & TM
resonances of DRs
H E
resonances of DRs• Features: Operational bands is narrow Adjustment
of DR resonant frequencies may be challengingTE011 mode TM011 mode
q y g g[1] C. L. Holloway et al., IEEE Trans. Antennas Propat.,
51, 2596, 2003
2) One-DR schemem p
Magnetic dipole Electric dipole)• Configuration: Mutual coupling• Features:
a) Wide operational band, compared to two-DR scheme
b) The operation is sensitive
HEM11δmode
b) The operation is sensitive to the arrangement of DRs .
[2] E. A. Semouchkina et al., IEEE Trans. MTT,53, 1477, 2005.
Microwave Electronics Lab
3) One-DR Scheme in Cut-Off Background• Configuration: Combination of TE-resonant DRs and negative
epsilon background composed of cut-off parallel-plate waveguide• Features:
a) Fabrication tolerance is large compared to two-DR schemeb) Effective epsilon and mu can be designed separately.[3] T. Ueda et al, 36th European Microwave Conference 2006, 435, 2006
H
E
Incident waveDR, εDR
Ehost medium, εBG
Effective permittivity of PPWG TE d
d < λg / 2 TE mode εeff,n = εBG [1-(ωc/ω)2 ] < 0 ωc = nπc / (εBG)1/2 d
Microwave Electronics Lab
ωc nπc / (εBG) d
Dispersion of 2D DR Array in Cutoff Waveguide
DR discεDR = 38a = 5.10 mmh = 2.03 mm
εBG = 2.2d = 5 00 mmd = 5.00 mmp = 6.00 mm
Microwave Electronics Lab
Dispersion of 2D DR Array in Cutoff Waveguide
DR discεDR = 38a = 5.10 mmh = 2.03 mm
εBG = 2.2d = 5 00 mmd = 5.00 mmp = 6.00 mm
Microwave Electronics Lab
Numerical Verification of Negative Refractionin 2 D RH LH RH structurein 2-D RH-LH-RH structure
In Region 2
εr = 10.2(RH)
In Region 2,there are 15 DRs.Beam propagationBeam propagation along ΓX
Incident angleθLH = 45 deg
Transmitted angleθLH = -25 deg
(LH) εr = 2.2
θLH 25 degat f = 10.8 GHz
εr = 10.2(RH)
Microwave Electronics Lab
r
Measured Field ProfilesFields were measured by a loop antenna as a magnetic probe at positions outside 5mm away from edge lines AQ and QB
peakpeak
Microwave Electronics LabRH prism inserted in Region 2 LH prism inserted in Region 2
Radiation Patterns (n = 15)( )Broadside
backfireendfire
f = 11.0GHz f = 11.1GHz
Array factor using damping constant α
f = 10.9GHz
y g p gFull-wave analysisMeasurement
Microwave Electronics Lab
Dispersion Diagram under Periodic Conditioni d PPWGwindow Along principal axis
εεDR
DR εDR PPWG
εBGεDR
εDR = 38a = 5.10 mmh = 2 03 mmh = 2.03 mmεBG = 2.2d = 4.00 mmp = 6.00 mm
Open window: 2mm x 2mmUnbalanced case
Microwave Electronics Lab
p
6 SIW CRLH6. SIW CRLH
Microwave Electronics Lab
Unit Cell Design and Analysis
(a) Equivalent circuit model for the SIW and HMSIW Transmission Lines
(b) Circuit model for CRLH Transmission Lines( )
Only the series capacitor is missing and needs to be introduced !
Microwave Electronics Lab
Only the series capacitor is missing and needs to be introduced !
Unit Cell Design and Analysis
CL: Interdigital CapacitorLL: From Via-walls
Si l I l t ti !
CR: Shunt Capacitance LR: Series Inductance
Proposed CRLH-based SIWHMSIW U it C ll D i
Simple Implementation !
The series capacitor (CL)
Microwave Electronics Lab
or HMSIW Unit Cell Design can be easily controlled.
Unit Cell Design and Analysis
Dispersion diagram of the CRLH SIW unit cells: Balanced
case and Unbalanced case are realized by choosing different slot
widths and lengths
Unwrapped S21 phase for the corresponding one- and three-stage
balanced CRLH SIW unit cells
Backward Wave
Microwave Electronics Lab
Backward Wave
CRLH SIW and HMSIW TLs
Measured and Simulated S-Simulated S
Parameters for the fabricated SIW andfabricated SIW and
CRLH-SIW TLs
Without changing the waveguideWithout changing the waveguidesize, the passband has been
extended to a lower frequency!
Microwave Electronics Lab
q y(from 7.4 GHz to 4.8 GHz )
7 Conclusions7. Conclusions
Microwave Electronics Lab
Conclusions
Transmission line approach of metamaterials
Nonresonant structures
with low losses and broad bandwidth
C t f it i ht/l ft h d d (CRLH) t i lConcept of composite right/left-handed (CRLH) material
Dispersion engineering capability p g g p y
Passive components and antennas with unique features
DR based and SIW based CRLH
Microwave Electronics Lab