current mirrors and current references
TRANSCRIPT
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Current Mirror and Current
Reference
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Introduction
Characteristic of Ideal Current MirrorDifferent Current Mirror Topologies
Simple Current Mirror (SCM)
Cascode Current Mirror (CCM)
Wide Swing Cascode Current Mirror (WSCCM)Self-Biased Wide Swing Cascode Current Mirror (SBWSCCM)
Wilson Current Mirror (WCM)
Regulated Cascode Current Mirror (RCCM)
Current Reference
Bootstrapped Current Reference
Supply Dependency
Start-up Issue
Stability
Outline
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Introduction
3
Current source defined by a resistive divider
I KW
L
R
R+ RVDD VTH
Ioutis significantly dependent on
supply voltage, processand temperature
A better approach is to copy current from areference current !
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A current mirror is basically nothing more than a current amplifier.
The ideal characteristics of a current mirror are:
Output current is linearly related to the input current (i= Ai).
Input resistance (R) is zero
Output resistance (R) is infinite.
In addition, we have the characteristic VMINwhich applies not only to the output but
also the input.
V is the range of input voltage over which the input resistance is not small.
V is the range of the output voltage over which the output resistance is not large
Characteristics of Current Mirror
4
Input characteristic Transfer characteristic Output characteristic
Graphically:
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Simple Current Mirror (SCM)
5
IEF= K
W
LV VTH
=
=
VD= V= V
V= VD V VTH
IEF= K
W
LV VTH
(1 + V)
I= K
W
LV VTH
(1 + V)
= VO
Influence of Channel-length Modulation
IdealSituation
VO+ VTH
R=1
g
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Small-signal Analysis of SCM
6
Calculation of Rin
v= V
r gv i = V
gV i=V
r
R=
=
1
+ 1
1
Calculation of Rout
v= v= 0
ri= V
R=V
i= r
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Mismatch in SCM
7
How can we reduce themismatch?
Large channel device
Matching layout
=
+
( + ) VD VDleads t1o poor current gain accuracy
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Cascode Current Mirror (CCM)
8
Large channel length (L) increases channel width (W)Output capacitance
of the current source increases
Solution: Use cascodetransistor to increase output resistance (Rout) !
44
M4shields node
Yfrom any
perturbation at
node P !
is chosen such that V= V V4 = V
V= V+ V4
(V3+ V)
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CCMcontinued
9
If
=
, then V3= V4and V= V
VOVO+ VTH
2VO+ 2VTH
2VO+ VTH
Headroom = 2 Overdrives + 1 Thresholds
R2
g
R
g
r
=
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CCMcontinued
10
M2enters into saturation
M4enters into saturation
Output characteristic
VD= VDleads accurate mirrored current
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Small-signal Analysis of CCM
11
Calculation of Rin(= , )
v= i gV r
v=ir
1 + gr
Similarly,
v3=ir3
1 + g3r3
v= v+ v3= i
r
1 + gr +
r3
1 + g3r3
R=v
i=
1
g r+
1
g3 r3
1
g+
1
g3
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Small-signal Analysis of CCM
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Calculation of Rout(= , )
v= r4 i g4v4
+r(i gv)
But, i= 0, v= v3= 0
v= 0; &
v4= v4= ir
v= i r+ r4 + g4r4ri
R=v
i
= r+ r4+ g4r4r g4r4r
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Wide-Swing Cascode CM (WSCCM)
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VO+ VTH
VO5+ VTH
Condition:VO5 VO+ VTH
M5is weaker than M1
2VO
R1
g
R g4r4r
Headroom = 2 Overdrives
Matched pairs
=
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Small-signal Analysis of WSCCM
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Calculation of Rin(= , )
Calculation of Rout Same as that of CCM
v= v
v= (ig3v3)r3+ v3
but, v3= 0 v3= v3
v= r3i+ (1 + g3r3)v3
but, v3= r(i gv)= r(i gv)
v= r3i+ (1 + g3r3)ri
gr 1 + g3r3 v
R=v
i=
r3+ 1 + g3r3 r
1 + gr 1 + g3r3
1
g
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CCM vs. WSCCM
15
CCM
WSCCM
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V+ IEFR
Condition:VO3 IEFR VTH
Headroom = 2 Overdrives
Self-Biased Wide-Swing Cascode CM (SBWSCCM)
2VO
V
R R +1
g
R g4r4r
=
Matched pairs
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Small-signal Analysis of SBWSCCM
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Calculation of Rin(= , )
Calculation of Rout Same as that of CCM
v= iR + r3 i g3v3
+r i gv
v= v iR and
v3= v r i gv
= v ri+ gr(v iR)
v= iR + r3i g3r3 v ri+ gr v iR
+r[i g(v+ iR)]
v 1 + g3r3+ grg3r3+ gr = iR + r+ r3+ g3r3r
+grg3r3R
R=v
i=
R + r+ r3+ g3r3r+ grg3r3R
1 + g3r3+ gg3r3+ gr R +
1
g
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Wilson Current Mirror (WCM)
18
WCM employs current-seriesnegative feedback
V
ID
+
-
=
( + )
[ + + ]
VD VDleads t1o poor current gain accuracy
Rg+ g3
gg3
R33
2VO+ VTH2(VO+ VTH)
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Regulated Cascode Current Mirror (RCCM)
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R g r
3
R1
g4
I
VV
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Comparison
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SCM poor VO VO+ VTH r1
g
CCM excellent 2VO+ VTH 2 VO+ VTH gr
2
g
WSCCM excellent 2VO VO+ VTH gr
1
g
SBWSCCM excellent 2VO VO+ VTH gr R +
1
g
WCM poor 2VO+ VTH 2VO+ VTH gr
1
g
RCCM good 2VO+ VTH VO+ VTH g r
31
g
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Current Reference
21
Current Source
Current Sink
1:K
1:K
V1V2
VDD= V4+ V
Considering, VD= VD V= V
V= Vh+2I
K W
L( 1 +V)
V3= Vh+2KI
K W4
L4 1 + VDD V
I= VDD
Problems:
Supply dependency
The current is not well-defined. The
circuit can support any arbitrary current
(at least, theoretically) as I= KIis
the only design equation
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Boot-strapped Current Reference
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V= Vh+2IEF
K W
L ( 1 +VD)
= Vh+2IEF
K
K
WL (1 + VD)
+ IEFR
IEFR =2
K W
L(1 + VD)
1 1
K
1 + VD
1 + VD
IEF= 12
K W
L(1 + VD)
1 1K
1 +( VD VD)
VDhas less supply dependency
VD= VDD V4; V4changes when VDDchanges.
But this change would be negligible if is less
Use long channel device
Cascode
K>1
aka -Mult ip l ier Circu it
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VX VY
VG
Supply Dependency
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VYVX
VG
Increasing the output resistance of short-
channel MOSFETs using feedback. The
result is better power supply sensitivity
A practical way of implementing
the error amplifier
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Degenerated Bias Point & Start-up Circuit
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Degenerated
bias point
Start-up Problem:The circuit can
latch to the degenerated bias pointBoot-strapped Current Referencewith Start-up Ckt.
This start-up circuit works for both
zeroand non-zero currents
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Stability of Boot-strapped Current Reference
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What type of feedback exists in the circuit?
V
V
V3
V4
It is a positive feedback !!!
Will the loop be stable?
Yes, because the loop-gain (LG) is less than one.
L.G.=V
V
V4
V=
g 1g4
1 + gR
g3
g
. . =
( + )< because, g< g
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Mismatch due to Body-bias Effect
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V= Vh+2IEF
K W
L(1 + VD)
= Vh+2IEF
K K
WL
(1 + VD)+ IEFR
Vh Vh
Threshold
increases due
to body-bias
Alternative implementation eliminating
body effect (possible in n-well process)
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Practical Applications
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Current Reference
NMOS Current Mirror
PMOS Current Mirror
R f
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1. B. Razavi, Design of Analog CMOS Integrated Circuits.
2. R. J. Baker, H. W. Li, and D. E. Boyce, CMOS Circuit Design, Layout, and Simulation.
3. P. E. Allen, and D. R. Holberg, CMOS Analog Circuit Design.
References
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