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AOE 5204
Linear Systems AnalysisLast time:
Axisymmetric, torque-free rigid bodyLinear equations, complete analytical solution
Asymmetric, torque-free rigid bodyNonlinear equations, analytical solution for angular velocities; linearized about principal axis spin
AOE 5204
Rigid Body Dynamics Equations of MotionThe complete set of coupled
translational and rotational equa-
tions of motion for a rigid body:
ω = I−1h
v =1
mp
f = f(r,v,R,ω)
g = g(r,v,R,ω)
r =1
mp− ω×r
p = −ω×p+ f˙q = Q(q)ω
h = −ω×h+ g
The differential equations are
coupled through ω, as well as
through the dependence of force
and moment on position, velocity,
attitude, and angular velocity
The force and moment can also
include controls; for example,
the torque on a submersible ve-
hicle can include environmental
torques due to viscosity, buoy-
ancy, and gravity, as well as con-
trol torques due to actuators such
as momentum wheels and fins
The equations are also nonlinear
AOE 5204
Control of Desired MotionsMany dynamics and control prob-
lems involve relatively simple,
steady motions
Examples
• straight and level flight of anairplane
• Earth-pointing attitude of a
satellite in a circular orbit
• straight and level motion of asubmersible vehicle
• straight motion of a surface ma-rine vessel
The nonlinear equations of mo-
tion are applicable
Disturbances affect the motion
(i.e., wind gusts, solar radiation
pressure, ocean currents, waves)
Controls are used to counter the
effects of the disturbances
Linearization about the desired
motion simplifies system analyis
and control synthesis
AOE 5204
Linear Systems Analysis and Control
•Linearization of the equations of motion•Stability analysis•Modal analysis•PID and LQR control synthesis•Controllability and observability•Stabilizability and detectability
AOE 5204
General Nonlinear System
The function f is sometimes
called the vector field
Often f will not depend on t, and
in that case the system is called
autonomous, or time-invariant
Furthermore, y usually does not
depend on u; if y does depend on
u, then the system is said to have
a feedforward connection between
the input and the output
Generally, the equations describ-
ing dynamics and control prob-
lems can be developed in the
form:
x = f(x,u, t)
y = g(x,u, t)
where x ∈ Rn, y ∈ Rm, and u ∈Rp
The vector x is the state vector,
the vector u is the input vector,
and the vector y is the output
vector
AOE 5204
Linearization
θ
Equations of motion for a pendu-
lum:
θ +g
lsin θ = 0
There is no input, but clearly
θ∗ = 0 and θ∗ = π are two equlib-
rium solutions
Using physical reasoning, we also
see that θ∗ = 0 is stable, whereas
θ∗ = π is unstable
Exercise
Suppose that there is some con-
stant input, u∗, and a constant
state vector, x∗, such that
x = f(x∗,u∗, t) = 0
This combination of input and
state is called an equilibrium,
since x = 0 implies that the state
remains constant
Dynamics and control analysts
are often interested in the stabil-
ity of equilibrium motions, and in
controlling motions near equilib-
rium motions
AOE 5204
Linearization (2)Define small perturbations away from the equilibrium state and
control:
x = x∗ + δx
u = u∗ + δu
Recall that for a scalar function f(x), the Taylor series is
f(x) = f(x∗ + δx)
= f(x∗) + f 0(x∗)δx+1
2!f 00(x∗)δx2 + · · ·
For the vector functions of vector arguments here, the Taylor series
is expressed similarly:
f(x) = f(x∗ + δx) = f(x∗) +∂f
∂x(x∗)δx+ · · ·
where the · · · represent the higher order terms in the Taylor series.
AOE 5204
Linearization (3)The vector field depends on x and u
x = f(x,u, t) = f(x∗ + δx,u∗ + δu, t)
Apply the Taylor series expansion to f(x,u, t) as
f(x,u, t) = f(x∗,u∗, t) +∂f
∂x(x∗,u∗, t)δx+
∂f
∂u(x∗,u∗, t)δu+ · · ·
By definition, the term f(x∗,u∗, t) = 0, so that the differential
equation is approximated as
˙δx =∂f
∂x(x∗,u∗, t)δx+
∂f
∂u(x∗,u∗, t)δu
The terms ∂f∂x (x
∗,u∗, t) and ∂f∂u(x
∗,u∗, t) are n× n and n× p ma-trices, respectively
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Linearization (4)
The first matrix in the linearized equation
˙δx =∂f
∂x(x∗,u∗, t)δx+
∂f
∂u(x∗,u∗, t)δu
is
∂f
∂x(x∗,u∗, t) =
⎡⎢⎣∂f1∂x1
· · · ∂f1∂xn
... · · ·...
∂fn∂x1
· · · ∂fn∂xn
⎤⎥⎦¯¯(x∗,u∗)
≡ A(t)
where the notation |(x∗,u∗) denotes that the terms in the matrixare evaluated at (x,u) = (x∗,u∗)
This matrix, A(t) is the plant matrix, or simply The Plant
If A(t) does not depend on t, then the system is a time-invariant,
or constant-coefficient system
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Linearization (5)
The second matrix in the linearized equation
˙δx =∂f
∂x(x∗,u∗, t)δx+
∂f
∂u(x∗,u∗, t)δu
is
∂f
∂u(x∗,u∗, t) =
⎡⎢⎢⎣∂f1∂u1
· · · ∂f1∂up
... · · ·...
∂fn∂u1
· · · ∂fn∂up
⎤⎥⎥⎦¯¯(x∗,u∗)
≡ B(t)
This matrix, B(t) is the input matrix
Using these matrix definitions, the linear equation can be written
˙δx = A(t)δx+B(t)δu
AOE 5204
Linearization (6)
The linearized equation
˙δx =∂f
∂x(x∗,u∗, t)δx+
∂f
∂u(x∗,u∗, t)δu
is abbreviated as˙δx = A(t)δx+B(t)δu
Frequently, the “δ” and the time-dependence are understood, and
the equation is written
x = Ax+Bu
This is a standard form for the linear state-space differential equa-
tion
One also sees
x = Fx+Gu
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Linearization (7)The “output” equation is handled similarly
y = g(x,u, t)
y∗ + δy = g(x∗ + δx,u∗ + δu, t)
δy =∂g
∂x(x∗,u∗, t)δx+
∂g
∂u(x∗,u∗, t)δu
δy = C δx+D δu
y = Cx+Du
Thus, the general nonlinear system
x = f(x,u, t)
y = g(x,u, t)
is approximated by
x = Ax+Bu
y = Cx+Du
AOE 5204
Linearization ExampleConsider the motion of a spinning rigid body with a constant
“environmental” torque. The desired motion of spinning body is
ω∗ = [Ω1 Ω2 Ω3]. We want to linearize the equations of motion
about the desired motion.
Expressed in a principal frame, the environmental torque is ge.
The “control” torque, g∗, required to maintain the desired motion
is easily computed using Euler’s equations:
ω = −I−1ω×Iω + I−1ge + I−1g = f(x,u)0 = −I−1ω∗×Iω∗ + I−1ge + I−1g∗ = f(x∗,u∗)g∗ = ω∗×Iω∗ − ge
Given the desired motion, ω∗ and the environmental torque ge, we
can easily compute g∗, which is clearly constant
In this problem, x = ω, u = g, x∗ = ω∗, and u∗ = g∗
AOE 5204
Linearization Example (2)Rosetta stone: x = ω, u = g, x∗ = ω∗, and u∗ = g∗
Equations in scalar form:
ω1 =I2 − I3I1
ω2ω3 +ge1I1+g1I1= f1(x,u)
ω2 =I3 − I1I2
ω1ω3 +ge2I2+g2I2= f2(x,u)
ω3 =I1 − I2I3
ω1ω2 +ge3I3+g3I3= f3(x,u)
The matrix, ∂f∂x (x∗,u∗, t), is
∂f
∂x(x∗,u∗, t) =
⎡⎢⎣ 0 I2−I3I1
Ω3I2−I3I1
Ω2I3−I1I2
Ω3 0 I3−I1I2
Ω1I1−I2I3
Ω2I1−I2I3
Ω1 0
⎤⎥⎦ ≡ AClearly A depends only on the inertias and the desired steady
motion ω∗.
AOE 5204
Linearization Example (3)Rosetta stone: x = ω, u = g, x∗ = ω∗, and u∗ = g∗
Equations of motion:
ω1 =I2 − I3I1
ω2ω3 +ge1I1+g1I1= f1(x,u)
ω2 =I3 − I1I2
ω1ω3 +ge2I2+g2I2= f2(x,u)
ω3 =I1 − I2I3
ω1ω2 +ge3I3+g3I3= f3(x,u)
The matrix ∂f∂u (x
∗,u∗, t) is
∂f
∂u(x∗,u∗, t) =
⎡⎣ 1I1
0 0
0 1I2
0
0 0 1I3
⎤⎦ ≡ BAs with A, the matrix B is constant and depends only on the
inertias. Note that B = I−1
AOE 5204
Linearization Example (4)Thus, the linearized equations of motion are
˙δω = A δω +B δg or x = Ax+Bu
where
A =
⎡⎢⎣ 0 I2−I3I1
Ω3I2−I3I1
Ω2I3−I1I2
Ω3 0 I3−I1I2
Ω1I1−I2I3
Ω2I1−I2I3
Ω1 0
⎤⎥⎦ and B =
⎡⎣ 1I1
0 0
0 1I2
0
0 0 1I3
⎤⎦Note that δω = ω−ω∗, and δg = g−g∗. A typical control problemis to determine the control δg that will maintain the desired motion
in the presence of initial condition errors and other disturbances.
A recommended exercise is to choose values of I, ge, and ω∗, and
then compare the results of integrating the nonlinear differential
equations with the results of integrating the linear equations.
AOE 5204
Stability AnalysisThe linearization process serves
to shift the origin to the equilib-
rium of interest
Before applying a control, we
should determine whether the
origin is stable in the absence of
any control (i.e., u = 0)
x = Ax
We further assume that A is con-
stant, so that we have a time-
invariant system
Stability analysis is based on the
eigenvalues of A
Consider the special case where
A is diagonal
The differential equation decou-
ples into the n first-order differ-
ential equations
x1 = A11x1
xj = Ajjxj
xn = Annxn
and each solution is immediately
integrable as
xj(t) = eAjjtxj(0)
Exercise: Solve for xj(t)
AOE 5204
Stability Analysis (2)If A is diagonal
xj(t) = eAjjtxj(0)
If Ajj < 0, then limt→∞ xj(t) = 0
If Ajj > 0, then limt→∞ xj(t) =
∞
Thus, Ajj < 0⇒ stability,
And Ajj > 0⇒ instability
If all states are stable, then the
system is stable.
If any of the states are unstable,
then the system is unstable.
The diagonal elements of a diago-
nal matrix are the eigenvalues of
the matrix, typically denoted
λj(A), j = 1, ..., n
For a diagonal matrix,
λj < 0∀ j ⇒ stability
λj > 0 for any j ⇒ instability
AOE 5204
Stability Analysis (3)More generally,A is not diagonal,
and its eigenvalues are either real,
or complex conjugate pairs
Denote the real and imaginary
parts of the eigenvalues by
Re λj and Im λj
The stability condition can then
be written as
Re λj < 0∀ j ⇒ stability
Re λj > 0 for any j ⇒ instabil-
ity
If any eigenvalue has Re λj = 0,
then the linear stability analysis
is inconclusive
We will develop the eigenvalue
decomposition next time
AOE 5204
Linearization ReviewThe general nonlinear system of equations is
x = f(x,u, t)
y = g(x,u, t)
where the state is x ∈ Rn, the input is u ∈ Rp, and the output isy ∈ Rm
Equilibrium motions, (x∗,u∗) satisfy
x = f(x∗,u∗, t) = 0
Linearization about (x∗,u∗), and simplifying notation with δx→ x
gives the linear system
x = Ax+Bu
y = Cx+Du
AOE 5204
State Feedback Control PreviewGeneral form for linear system is
x = Ax+Bu
y = Cx+Du
A standard control application is to let the input depend on the
state:
u = −Kx
With this form for the input, the state dynamics equation becomes
x = Ax−BKx= [A−BK]x= Ax
As we continue with linear stability analysis, keep in mind that the
analysis of x = Ax is equally applicable to x = Ax
AOE 5204
Stability AnalysisThe linearization process serves
to shift the origin to the equilib-
rium of interest
Before applying a control, we
should determine whether the
origin is stable in the absence of
any control (i.e., u = 0)
x = Ax
We further assume that A is con-
stant, so that we have a time-
invariant system
Stability analysis is based on the
eigenvalues of A
Consider the special case where
A is diagonal
The differential equation decou-
ples into the n first-order differ-
ential equations
x1 = A11x1
xj = Ajjxj
xn = Annxn
and each solution is immediately
integrable as
xj(t) = eAjjtxj(0)
Exercise: Solve for xj(t)
AOE 5204
Stability Analysis (2)If A is diagonal
xj(t) = eAjjtxj(0)
If Ajj < 0, then limt→∞ xj(t) = 0
If Ajj > 0, then limt→∞ xj(t) =
∞
Thus, Ajj < 0⇒ stability,
And Ajj > 0⇒ instability
If all states are stable, then the
system is stable.
If any of the states are unstable,
then the system is unstable.
The diagonal elements of a diago-
nal matrix are the eigenvalues of
the matrix, typically denoted
λj(A), j = 1, ..., n
For a diagonal matrix,
λj < 0∀ j ⇒ stability
λj > 0 for any j ⇒ instability
AOE 5204
Stability Analysis (3)More generally,A is not diagonal,
and its eigenvalues are either real,
or complex conjugate pairs
Denote the real and imaginary
parts of the eigenvalues by
Re λj and Im λj
The stability condition can then
be written as
Re λj < 0∀ j ⇒ stability
Re λj > 0 for any j ⇒ instabil-
ity
If any eigenvalue has Re λj = 0,
then the linear stability analysis
is inconclusive
We will develop the eigenvalue
decomposition next time
AOE 5204
Eigenvalue Decomposition of AWork with the zero-input state dynamics equation
x = Ax
Assume solutions of the form
x(t) = eλte, with constants λ ∈ C, e ∈ Cn
Substitute into the differential equation, and obtain
λeλte = Aeλte
The scalar, eλt can never be zero, so
λe = Ae
[λ1−A] e = 0
det [λ1−A] = 0
p(λ) = 0 characteristic polynomial
AOE 5204
Eigenvalue Decomposition of A (2) Working with the zero-input state dynamics equation
x = Ax, x(t) = eλte
Leads to
det [λ1−A] = 0
p(λ) = 0 characteristic polynomial
Example:
A =
∙1 2−1 6
¸⇒ [λ1−A] =
∙λ− 1 −21 λ− 6
¸det [λ1−A] = 0 ⇒ p(λ) = (λ− 1)(λ− 6) + 2 = 0λ2 − 7λ+ 8 = 0 ⇒ λ = 5.5616, 1.4384
Matlab: eig([1 2; -1 6]) and roots([1 -7 8]) both give
this result.
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Eigenvalue Decomposition of A (3) Generally, there are n eigenvalues (roots of the characteristic poly-
nomial), and they are distinct
There can be repeated eigenvalues
Eigenvalues can be real or complex; if complex, they always come
in complex conjugate pairs
If the eigenvalues are distinct, then there are n linearly independent
eigenvectors, ej , one associated with each eigenvalue, λj
Linear independence means that no eigenvector can be written as
a linear combination of the remaining eigenvectors
With n linearly independent eigenvectors, any vector x ∈ Rn canbe written as a linear combination of the eigenvectors:
x =nXj=1
cjej
AOE 5204
Eigenvalue Decomposition of A (4) Each eigenvalue-eigenvector pair satisfies
Aej = λjej
We can rewrite as (Exercise)
A[e1 · · · en] = [e1 · · · en] diag[λ1 · · ·λn]⇒ AE = EΛ
Since the eigenvectors are linearly independent, the matrix E is
non-singular, so
A = EΛE−1
Thus, we have factored the matrix A into the product of three
matrices, one of which is diagonal (for distinct eigenvalues)
This factorization is called the eigenvalue decomposition; there are
other matrix decompositions
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Eigenvalue Decomposition of A (5) We are still assuming distinct eigenvalues, in which case
A = EΛE−1
where E is the eigenvector matrix and Λ is the diagonal eigenvalue
matrix
Recall the assumed form of the solution to x = Ax:
xj(t) = eλjtej
Since the eigenvectors are linearly independent, any solution can
be written as a linear combination of these n solutions:
x(t) =nXj=1
cjeλjtej
where the constants cj depend on the initial conditions
AOE 5204
Eigenvalue Decomposition of A (5)
The general solution to x = Ax is
x(t) =nXj=1
cjeλjtej
where the constants cj depend on the initial conditions
We can rewrite the summation as (Exercise):
x(t) = E diag£eλ1t · · · eλjt · · · eλnt
¤c = EeΛtc = EeΛtE−1x(0)
Note the similarity in the eigenvalue decomposition of A and its
application to the solution:
A = EΛE−1
x(t) = EeΛtE−1x(0)
AOE 5204
Eigenvalue Decomposition of A (6)
For constant A with distinct eigenvalues, we have
A = EΛE−1
x(t) = EeΛtE−1x(0)
Where Λ is the diagonal eigenvalue matrix, E is the eigenvector
matrix, and x(0) is the initial state
Premultiply the solution by E−1 to obtain
E−1x(t) = eΛtE−1x(0)
Notice that E−1x appears on both sides. Define z(t) = E−1x(t),
and obtain
z(t) = eΛtz(0) z = Λz
Thus, for the constant-coefficient case, ifA has distinct eigenvalues,
we can transform the system to a decoupled system
AOE 5204
Eigenvalue Decomposition Example
A =
⎡⎣ −2 −1 1−0.5 −2.5 0.50.5 −0.5 −1.5
⎤⎦ Matlab: [E,Lambda]=eig(A)
Λ =
⎡⎣ −3 0 00 −1 00 0 −2
⎤⎦E =
⎡⎣ 0.7071 −0.7071 00.7071 0 0.7071
0 −0.7071 0.7071
⎤⎦Matlab check: E*Lambda*inv(E) should = A
Initial conditions
x(0) = [2 − 3 1]T
z(0) = E−1[2 − 3 1]T Matlab: z0 = E\x0z(0) = [−1.4142 − 4.2426 − 2.8284]T
AOE 5204
Eigenvalue Decomposition Example (2)
Started with
A =
⎡⎣ −2 −1 1−0.5 −2.5 0.50.5 −0.5 −1.5
⎤⎦Found the eigensystem. Transformed initial conditions from x(0)
to z(0). Now we can write the solution as
z(t) = z1(0)e−3t
⎡⎣ 100
⎤⎦+ z2(0)e−1t⎡⎣ 010
⎤⎦+ z3(0)e−2t⎡⎣ 001
⎤⎦or
x(t) = c1e−3t
⎡⎣ 0.70710.70710
⎤⎦+c2e−1t⎡⎣ −0.70710−0.7071
⎤⎦+c3e−2t⎡⎣ 00.70710.7071
⎤⎦
AOE 5204
Complex λ Eigenvalue Example
A =
⎡⎣ −1 0 00 3 −20 5 −3
⎤⎦ Λ =
⎡⎣ i 0 00 −i 00 0 −1
⎤⎦E =
⎡⎣ 0 0 10.5071 + 0.1690i 0.5071− 0.1690i 0
0.8452 0.8452 0
⎤⎦Λ is diagonal, but it is also complex. We can create a block-diagonal
matrix and block-diagonal eigenvalue matrix as follows
Eb = [Re e1 Im e1 e3]
=
⎡⎣ 0 0 10.5071 0.1690 00.8452 0 0
⎤⎦Λb = E−1b AEb
=
⎡⎣ 0 1 0−1 0 00 0 −1
⎤⎦
AOE 5204
Complex λ Eigenvalue Example (2)System is block-diagonalized. Not quite as good as diagonal, but
better than nothing.
Eb =
⎡⎣ 0 0 10.5071 0.1690 00.8452 0 0
⎤⎦Λb =
⎡⎣ 0 1 0−1 0 00 0 −1
⎤⎦x(t) = Ebe
ΛbtE−1b x(0)
What is eΛbt? It turns out to be
eΛbt =
⎡⎣ cos t sin t 0− sin t cos t 0
0 0 e−t
⎤⎦
AOE 5204
Complex λ Eigenvalue Example (3)
x(t) = EbeΛbtE−1b x(0)
where
eΛbt =
⎡⎣ cos t sin t 0− sin t cos t 0
0 0 e−t
⎤⎦
z(t) = E−1b x(t)
z(t) = eΛbtz(0)
z(t) = z1(0)
⎡⎣ cos t− sin t
0
⎤⎦+ z2(0)⎡⎣ sin tcos t0
⎤⎦+ z3(0)⎡⎣ 0
0e−t
⎤⎦+The block-diagonalization procedure works for complex eigenvalues
of the form σ + ωi, and makes use of Euler’s identity:
eσ+ωi = eσeωieσ (cosω + i sinω)
AOE 5204
Linear Systems AnalysisLast time:
Review of linearization about equilibrium motions
Diagonal systems
Eigenvalue decomposition
Diagonalization and block-diagonalization
AOE 5204
Eigenvalue Decomposition of AIf A ∈ Rn×n has distinct eigenvalues, then we can factor A into
the product of three matrices:
A = EΛE−1
where Λ is the diagonal matrix of eigenvalues, and E is the matrix
of linearly independent eigenvectors.
In general, Λ ∈ Cn×n, and E ∈ Cn×n
With the eigenvalue decomposition, we can write
eAt = EeΛtE−1
The advantage of this formulation of the matrix exponential is that
eΛt = diag£eλ1t eλjt eλnt
¤T
AOE 5204
Zero-Input SolutionThe solution to the differential equation
x = Ax
is
x(t) = eAtx(0) = EeΛtE−1x(0)
Decoupled system dynamics is obtained by transforming from x to
z
E−1x(t) = eΛtE−1x(0)
z(t) = eΛtz(0)
If Λ and E are complex, then a real-valued partial decoupling is
possible by defining Eb and Λb; e.g.
Eb = [Ree1 Ime1 e3] , Λb = E−1b AEb
AOE 5204
Block Diagonalization ProcedureIf A has complex eigenvalues and eigenvectors, they always come
in complex conjugate pairs: λj,j+1 = σ ± iω, ej,j+1 = Reej ±iImej For each c.c. pair of eigenvalues and eigenvectors, replaceeigenvectors (j and j + 1 columns of E) with Reej and Imej;e.g.
Eb = [Ree1 Ime1 e3]
Then form the block-diagonal eigenvalue matrix using
Λb = E−1b AEb
The 2× 2 blocks of Λb associated with the complex conjugate pairwill always be in the form ∙
σ ω−ω σ
¸Diagonal blocks associated with real eigenvalues are unaffected
AOE 5204
Eigenvalue Recognition: Pop QuizWhat are the eigenvalues of the following matrices?
(a)
∙1 00 −3
¸(b)
∙1 02 −3
¸(c)
∙1 40 −3
¸
(d)
⎡⎣ 1 0 00 −3 00 0 7
⎤⎦ (e)
⎡⎣ 1 0 011 −3 03 1 7
⎤⎦ (f)
⎡⎣ 1 11 30 −3 10 0 7
⎤⎦What are the roots of the following characteristic polynomials?
(g) λ2 + 3λ+ 2
(h) λ(λ2 + 3λ+ 2)
(i) (λ+ 2)(λ+ 1)
(j) λ(λ+ 2)(λ+ 1)
(k) (λ+ 7)(λ+ 2)(λ+ 1)
(l) (λ+ 7)(λ+ 2)(λ+ 1)(λ− 3)(λ− 9)
AOE 5204
Matrix Exponential and Matrix FunctionsThe matrix exponential eAt is defined so that its Taylor series is in
the same form as that for the scalar exponential
eat = 1 + at+1
2!a2t2 +
1
3!a3t3 + · · · 1
n!antn + · · ·
eAt = 1+At+1
2!A2t2 +
1
3!A3t3 + · · · 1
n!Antn + · · ·
The Cayley-Hamilton Theorem: A matrix A satisfies its own char-
acteristic polynomial:
p(λ) = λn + an−1λn−1 + · · ·+ a1λ+ a0 = 0
p(A) = An + an−1An−1 + · · ·+ a1A+ a01 = 0
Example application: Multiply p(A) by A−1 and solve for A−1:
A−1 = − 1a0
£An−1 + an−1A
n−2 + · · ·+ a11¤
AOE 5204
Matrix Exponential ExamplesTaylor series for scalar and matrix exponentials:
eat = 1 + at+1
2!a2t2 +
1
3!a3t3 + · · · 1
n!antn + · · ·
eAt = 1+At+1
2!A2t2 +
1
3!A3t3 + · · · 1
n!Antn + · · ·
Compute the exponential of a 2× 2 diagonal matrix.
A =
∙a1 00 a2
¸eAt = 1+At+
1
2!A2t2 +
1
3!A3t3 + · · · 1
n!Antn + · · ·
=
∙1 00 1
¸+
∙a1 00 a2
¸t+
1
2!
∙a1 00 a2
¸2t2 +
1
3!
∙a1 00 a2
¸3t3 + · · ·
=
∙1 + a1t+
12!a
21t2 + 1
3!a31t3 + · · · 0
0 1 + a2t+12!a
22t2 + 1
3!a32t3 + · · ·
¸=
∙ea1t 00 ea2t
¸
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Matrix Exponential Examples (2)Compute the exponential of a 2×2 block-diagonal matrix,A =
∙0 ω−ω 0
¸
eAt = 1+At+1
2!A2t2 +
1
3!A3t3 + · · · 1
n!Antn + · · ·
=
∙1 00 1
¸+
∙0 ω−ω 0
¸t+
1
2!
∙0 ω−ω 0
¸2t2 +
1
3!
∙0 ω−ω 0
¸3t3 + · · ·
=
∙1 00 1
¸+
∙0 ω−ω 0
¸t+
1
2!
∙−ω2 00 −ω2
¸t2 +
1
3!
∙0 −ω3ω3 0
¸t3 + · · ·
=
∙1− 1
2!ω2t2 + · · · ωt− 1
3!ω3t3 + · · ·
−ωt+ 13!ω
3t3 + · · · 1− 12!ω
2t2 + · · ·
¸=
∙cosωt sinωt− sinωt cosωt
¸
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Matrix Exponential Examples (3)Consider complex conjugate eigenvalues λ1,2 = σ ± iω
The 2× 2 block of Λb is
A =
∙σ ω−ω σ
¸Instead of Taylor series, apply eAt = EeΛtE−1
The eigenvector matrix and its inverse are
E =
∙1 1i −i
¸and E−1 =
∙1/2 −i/21/2 i/2
¸Note that these eigenvectors are not normalized, nor is
normalization of eigenvectors required
The exponential term is
eΛt =
∙e(σ+iω)t 00 e(σ−iω)t
¸
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Matrix Exponential Examples (4)Continuing with c.c. eigenvalues λ1,2 = σ ± iω
The diagonalized matrix exponential term is
eΛt =
∙e(σ+iω)t 00 e(σ−iω)t
¸Recall that e(σ+iω)t = eσt(cosωt+ i sinωt)
Carrying out the required matrix multiplication leads to
eAt = exp
∙σ ω−ω σ
¸t
=
∙1 1i −i
¸ ∙eσt(cosωt+ i sinωt) 0
0 eσt(cosωt− i sinωt)t
¸×∙
1/2 −i/21/2 i/2
¸=
∙cosωt sinωt− sinωt cosωt
¸eσt
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Matrix Exponential Examples (5)An example with 5 eigenvalues: one real, λ1; two pure imaginary,
λ2,3 = ±iω1; and two complex conjugates, λ4,5 = σ ± iω2
Λb =
⎡⎢⎢⎢⎢⎣λ1 0 0 0 00 0 ω1 0 00 −ω1 0 0 00 0 0 σ ω20 0 0 −ω2 σ
⎤⎥⎥⎥⎥⎦
eΛbt =
⎡⎢⎢⎢⎢⎣eλ1t 0 0 0 00 cosω1t sinω1t 0 00 − sinω1t cosω1t 0 00 0 0 eσt cosω2t eσt sinω2t0 0 0 −eσt sinω2t eσt cosω2t
⎤⎥⎥⎥⎥⎦Any matrix A that has these five eigenvalues will have this block
diagonal structure
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Cayley-HamiltonThe Cayley-Hamilton Theorem: A matrix A satisfies its own char-
acteristic polynomial:
p(A) = An + an−1An−1 + · · ·+ a1A+ a01 = 0
Example application: Multiply p(A) by A−1 and solve for A−1:
A−1 = − 1a0
£An−1 + an−1A
n−2 + · · ·+ a11¤
A 2× 2 example: A =
∙1 2−1 6
¸, p(λ) = λ2 − 7λ+ 8 = 0
A−1 = −18
½∙1 2−1 6
¸− 7∙1 00 1
¸¾=
∙0.7500 −0.25000.1250 0.1250
¸Exercise: check this calculation with Matlab, and try the procedure
on some matrices with larger n
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Another Cayley-Hamilton ApplicationSince A satisfies its own characteristic polynomial,
p(A) = An + an−1An−1 + · · ·+ a1A+ a01 = 0
every higher order power of A can be written as a linear combina-
tion of 1,A,A2, · · ·An−1
A useful application of this fact is the expression of eAt:
eAt = 1+At+1
2!A2t2 + · · ·
= α0(t)1+ α1(t)A+ α2(t)A2 + · · ·+ αn−1(t)A
n−1
=n−1Xj=0
αj(t)Aj
where the αj(t) terms are independent functions of time
We can calculate the αj(t) functions, but the most useful applica-
tion of this expression is in the development of the conditions for
controllability and observability
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Modal AnalysisWe have already seen the modal decomposition that arises when
we diagonalize or block-diagonalize a linear system
A more detailed example:
A =
⎡⎣ 4 −6 −12 −1 −14 −4 −4
⎤⎦has eigenvalues (−3.6252, 1.3126 ± i1.9478) (stable or unstable?),and eigenvectors
E =
⎡⎣ 0.2565 −0.8154 −0.81540.1673 −0.2967 + i0.2740 −0.2967− i0.27400.9520 −0.4109− i0.0556 −0.4109 + i0.0556
⎤⎦Block-diagonalize by defining
Eb = [e1 Ree2 Ime2] and Λb = E−1b AEb
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Modal Analysis (2)
A =
⎡⎣ 4 −6 −12 −1 −14 −4 −4
⎤⎦ Λ = diag
⎡⎣ −3.62521.3126 + i1.94781.3126− i1.9478
⎤⎦
E =
⎡⎣ 0.2565 −0.8154 −0.81540.1673 −0.2967 + i0.2740 −0.2967− i0.27400.9520 −0.4109− i0.0556 −0.4109 + i0.0556
⎤⎦
Eb =
⎡⎣ 0.2565 −0.8154 00.1673 −0.2967 0.27400.9520 −0.4109 −0.0556
⎤⎦Λb =
⎡⎣ −3.6252 0 00 1.3126 1.94780 −1.9478 1.3126
⎤⎦We can use x, z, or zb
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Modal Analysis (3)
x = Ax, z = Λz, zb = Λbzb
x is coupled; z is completely decoupled; zb is partially decoupled
With x, one cannot easily see how the three states relate to the
eigenvalues and eigenvectors
With z, the fact that two states are complex-valued makes it diffi-
cult to understand the dynamics
With zb, the coupling between z2 and z3 is natural and easily un-
derstood
Consider the initial condition x(0) = [1 0 0]T
Note that the period of the oscillatory motion is T = 2π/ω, where
ω is the imaginary part of the eigenvalue
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Modal Analysis (4)
0 0.5 1 1.5 2 2.5 3 3.5−40
−20
0
20
40
60
80
100
t
x
x1
x2
x3
Initial state is x(0) = [1 0 0]T . Even though x2(0) = x3(0), all
three states diverge due to the coupling and the instability
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Modal Analysis (5)
0 0.5 1 1.5 2 2.5 3 3.5−100
−80
−60
−40
−20
0
20
40
t
z
z1
z2
z3
Initial state is x(0) = [1 0 0]T ⇒ z(0) = [−0.6897 − 1.4433 −1.1421]T . The state associated with the stable eigenvalue is not
unstable
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Modal Analysis (6)
0 0.5 1 1.5 2 2.5 3 3.5−0.7
−0.6
−0.5
−0.4
−0.3
−0.2
−0.1
0
0.1
t
z
z1
z2
z3
Initial state is z(0) = [−0.6897 0 0]T , corresponding to the stable
mode. The other states remain zero
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Modal Analysis (7)
0 0.5 1 1.5 2 2.5 3 3.5−100
−80
−60
−40
−20
0
20
40
t
z
z1
z2
z3
Initial state is z(0) = [0 − 1.4433 − 1.1421]T , corresponding tothe unstable mode. The other state remains zero
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Modal Analysis (8)
Modal analysis is based on block-diagonalizing x = Ax to obtain
zb = Λbzb
Whereas x is coupled, zb is partially decoupled
The real eigenvalues have one-dimensional real modes with expo-
nential (aka first-order) behavior
The complex conjugate eigenvalues have two-dimensional real
modes with exponential+oscillatory (aka second-order) behavior
By decomposing the motion into different modes, we can determine
the behavior of a dynamic system and focus attention on specific
modes of interest
Typically unstable, marginally stable, or barely stable modes are of
the most interest
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Back to the SolutionThe solution to the differential equation x = Ax is x(t) =
eAtx(0) = EeΛtE−1x(0), but what about
x = Ax+Bu ?
Consider the n = p = 1 case
x = ax+ u ⇒ x− ax = u
where a is constant and u is time-varying
One way to solve this first-order ODE is to turn the left-hand side
into a total derivative
Multiply by an unknown function y(t) and determine the form of
y(t) so that the left-hand side is d(xy)/dt
xy − axy = d
dt(xy) = xy + xy
AOE 5204
Back to the Solution (2)
We are seeking y(t) so that
xy − axy = d
dt(xy) = xy + xy
Subtract xy from both sides to obtain
−axy = xy ⇒ −ay = y ⇒ y(t) = e−aty(0)
Choose y(0) = 1, so y(t) = e−at
Now, back to the original differential equation (with y(t) in it):
d
dt(xy) = uy ⇒ d(xy) = uy dtZ (·)(t)
(·)(0)d(xy) =
Z t
0
uy(τ) dτ
x(t)y(t)− x(0)y(0) =
Z t
0
uy(τ) dτ
AOE 5204
Back to the Solution (2)
x(t)y(t)− x(0)y(0) =
Z t
0
uy(τ) dτ
x(t)e−at − x(0) =
Z t
0
ue−aτ dτ
x(t)e−at = x(0) +
Z t
0
ue−aτ dτ
x(t) = eatx(0) + eatZ t
0
ue−aτ dτ
The form of the solution for general n and p is the same as above:
x(t) = eAtx(0) + eAtZ t
0
e−AτBu(τ) dτ
The first term is the zero-input solution, and the second term isthe zero-state solution:
x(t) = xzi(t) + xzs(t)
AOE 5204
Controllability and Observability
The general solution to x = Ax+Bu is
x(t) = eAtx(0) + eAtZ t
0
e−AτBu(τ) dτ
The first term is the zero-input solution, and the second term isthe zero-state solution:
x(t) = xzi(t) + xzs(t)
Controllability. Does a control exist such that xzs(tf ) = xf forany xf and finite tf? If yes, then the system is controllable.
The output equation is y = Cx+Du
Observability. Does an initial state x(0) exist such that the zero-input solution produces identically zero output? If so, then thesystem is unobservable.
AOE 5204
Linear Systems AnalysisLast time:
Diagonalization and block-diagonalization
Eigenvalue recognition
Cayley-Hamilton Theorem
Matrix Exponential
AOE 5204
Another Cayley-Hamilton ApplicationSince A satisfies its own characteristic polynomial,
p(A) = An + an−1An−1 + · · ·+ a1A+ a01 = 0
every higher order power of A can be written as a linear combina-
tion of 1,A,A2, · · ·An−1
A useful application of this fact is the expression of eAt:
eAt = 1+At+1
2!A2t2 + · · ·
= α0(t)1+ α1(t)A+ α2(t)A2 + · · ·+ αn−1(t)A
n−1
=n−1Xj=0
αj(t)Aj
where the αj(t) terms are independent functions of time
We can calculate the αj(t) functions, but the most useful applica-
tion of this expression is in the development of the conditions for
controllability and observability
AOE 5204
Modal AnalysisWe have already seen the modal decomposition that arises when
we diagonalize or block-diagonalize a linear system
A more detailed example:
A =
⎡⎣ 4 −6 −12 −1 −14 −4 −4
⎤⎦has eigenvalues (−3.6252, 1.3126 ± i1.9478) (stable or unstable?),and eigenvectors
E =
⎡⎣ 0.2565 −0.8154 −0.81540.1673 −0.2967 + i0.2740 −0.2967− i0.27400.9520 −0.4109− i0.0556 −0.4109 + i0.0556
⎤⎦Block-diagonalize by defining
Eb = [e1 Ree2 Ime2] and Λb = E−1b AEb
AOE 5204
Modal Analysis (2)
A =
⎡⎣ 4 −6 −12 −1 −14 −4 −4
⎤⎦ Λ = diag
⎡⎣ −3.62521.3126 + i1.94781.3126− i1.9478
⎤⎦
E =
⎡⎣ 0.2565 −0.8154 −0.81540.1673 −0.2967 + i0.2740 −0.2967− i0.27400.9520 −0.4109− i0.0556 −0.4109 + i0.0556
⎤⎦
Eb =
⎡⎣ 0.2565 −0.8154 00.1673 −0.2967 0.27400.9520 −0.4109 −0.0556
⎤⎦Λb =
⎡⎣ −3.6252 0 00 1.3126 1.94780 −1.9478 1.3126
⎤⎦We can use x, z, or zb
AOE 5204
Modal Analysis (3)
x = Ax, z = Λz, zb = Λbzb
x is coupled; z is completely decoupled; zb is partially decoupled
With x, one cannot easily see how the three states relate to the
eigenvalues and eigenvectors
With z, the fact that two states are complex-valued makes it diffi-
cult to understand the dynamics
With zb, the coupling between z2 and z3 is natural and easily un-
derstood
Consider the initial condition x(0) = [1 0 0]T
Note that the period of the oscillatory motion is T = 2π/ω, where
ω is the imaginary part of the eigenvalue
AOE 5204
Modal Analysis (4)
0 0.5 1 1.5 2 2.5 3 3.5−40
−20
0
20
40
60
80
100
t
x
x1
x2
x3
Initial state is x(0) = [1 0 0]T . Even though x2(0) = x3(0), all
three states diverge due to the coupling and the instability
AOE 5204
Modal Analysis (5)
0 0.5 1 1.5 2 2.5 3 3.5−100
−80
−60
−40
−20
0
20
40
t
z
z1
z2
z3
Initial state is x(0) = [1 0 0]T ⇒ z(0) = [−0.6897 − 1.4433 −1.1421]T . The state associated with the stable eigenvalue is not
unstable
AOE 5204
Modal Analysis (6)
0 0.5 1 1.5 2 2.5 3 3.5−0.7
−0.6
−0.5
−0.4
−0.3
−0.2
−0.1
0
0.1
t
z
z1
z2
z3
Initial state is z(0) = [−0.6897 0 0]T , corresponding to the stable
mode. The other states remain zero
AOE 5204
Modal Analysis (7)
0 0.5 1 1.5 2 2.5 3 3.5−100
−80
−60
−40
−20
0
20
40
t
z
z1
z2
z3
Initial state is z(0) = [0 − 1.4433 − 1.1421]T , corresponding tothe unstable mode. The other state remains zero
AOE 5204
Modal Analysis (8)
Modal analysis is based on block-diagonalizing x = Ax to obtain
zb = Λbzb
Whereas x is coupled, zb is partially decoupled
The real eigenvalues have one-dimensional real modes with expo-
nential (aka first-order) behavior
The complex conjugate eigenvalues have two-dimensional real
modes with exponential+oscillatory (aka second-order) behavior
By decomposing the motion into different modes, we can determine
the behavior of a dynamic system and focus attention on specific
modes of interest
Typically unstable, marginally stable, or barely stable modes are of
the most interest
AOE 5204
Back to the SolutionThe solution to the differential equation x = Ax is x(t) =
eAtx(0) = EeΛtE−1x(0), but what about
x = Ax+Bu ?
Consider the n = p = 1 case
x = ax+ u ⇒ x− ax = u
where a is constant and u is time-varying
One way to solve this first-order ODE is to turn the left-hand side
into a total derivative
Multiply by an unknown function y(t) and determine the form of
y(t) so that the left-hand side is d(xy)/dt
xy − axy = d
dt(xy) = xy + xy
AOE 5204
Back to the Solution (2)
We are seeking y(t) so that
xy − axy = d
dt(xy) = xy + xy
Subtract xy from both sides to obtain
−axy = xy ⇒ −ay = y ⇒ y(t) = e−aty(0)
Choose y(0) = 1, so y(t) = e−at
Now, back to the original differential equation (with y(t) in it):
d
dt(xy) = uy ⇒ d(xy) = uy dtZ (·)(t)
(·)(0)d(xy) =
Z t
0
uy(τ) dτ
x(t)y(t)− x(0)y(0) =
Z t
0
uy(τ) dτ
AOE 5204
Back to the Solution (2)
x(t)y(t)− x(0)y(0) =
Z t
0
uy(τ) dτ
x(t)e−at − x(0) =
Z t
0
ue−aτ dτ
x(t)e−at = x(0) +
Z t
0
ue−aτ dτ
x(t) = eatx(0) + eatZ t
0
ue−aτ dτ
The form of the solution for general n and p is the same as above:
x(t) = eAtx(0) + eAtZ t
0
e−AτBu(τ) dτ
The first term is the zero-input solution, and the second term isthe zero-state solution:
x(t) = xzi(t) + xzs(t)
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Controllability and Observability
The general solution to x = Ax+Bu is
x(t) = eAtx(0) + eAtZ t
0
e−AτBu(τ) dτ
The first term is the zero-input solution, and the second term isthe zero-state solution:
x(t) = xzi(t) + xzs(t)
Controllability. Does a control exist such that xzs(tf ) = xf forany xf and finite tf? If yes, then the system is controllable.
The output equation is y = Cx+Du
Observability. Does an initial state x(0) exist such that the zero-input solution produces identically zero output? If so, then thesystem is unobservable.
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ControllabilityThe zero-state solution to x = Ax+Bu is
xzs(t) = eAtZ t
0
e−AτBu(τ) dτ
Controllability. Does a control exist such that xzs(tf ) = xf forany xf and finite tf? If yes, then the system is controllable.
Keep in mind that x ∈ Rn, u ∈ Rp, A ∈ Rn×n, and B ∈ Rn×p
Also recall that the Cayley-Hamilton Theorem leads to
eAt =n−1Xj=0
αj(t)Aj
where the αj(t) terms are independent functions of time
Remember, the question is: Can we get from zero to anywhere infinite time?
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Controllability (2)Consider the system with
A =
∙1 00 3
¸, B =
∙01
¸Since the system is diagonal, the dynamics are decoupled and thetwo states are governed by
x1 = x1 and x2 = 3x2 + u
The control has no effect on x1; thus x1 is uncontrollable. Thereis no control u that can drive x1 to any non-zero value in finite (oreven infinite) time.
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Controllability (3)One way to add controllability to the problem in the previous ex-ample is to modify the B matrix
Consider the system with
A =
∙1 00 3
¸, B =
∙11
¸Since the system is diagonal, the dynamics are decoupled and thetwo states are governed by
x1 = x1 + u and x2 = 3x2 + u
The control affects both states, and, as we show later, the systemis controllable
Controllability depends on A and B
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Controllability (4)The zero-state solution to x = Ax+Bu is
xzs(t) = eAtZ t
0
e−AτBu(τ) dτ
and we want to determine whether any xzs(t) is possible.
xzs(t) = eAtZ t
0
e−AτBu(τ) dτ
=
Z t
0
eA(t−τ)Bu(τ) dτ
Recall that Cayley-Hamilton leads to
eAt =n−1Xj=0
αj(t)Aj
Substitute this sum into the integral
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Controllability (5)
xzs(t) =n−1Xj=0
Z t
0
αj(t− τ)AjBu(τ) dτ
=n−1Xj=0
AjB
Z t
0
αj(t− τ)u(τ) dτ
=n−1Xj=0
Aj
∙b1
Z t
0
αj(t− τ)u1(τ) dτ+
b2
Z t
0
αj(t− τ)u2(τ) dτ + · · ·+
bp
Z t
0
αj(t− τ)up(τ) dτ¸
The integrals are functions of t:
γjk(t) =
Z t
0
αj(t− τ)uk(τ) dτ, k = 1, · · · , p
AOE 5204
Controllability (6)
xzs(t) =n−1Xj=0
Aj
∙b1
Z t
0
αj(t− τ)u1(τ) dτ+
b2
Z t
0
αj(t− τ)u2(τ) dτ + · · ·+
bp
Z t
0
αj(t− τ)up(τ) dτ¸
The integrals are functions of t:
γjk(t) =
Z t
0
αj(t− τ)uk(τ) dτ, k = 1, · · · , p
The zero-state solution is
xzs(t) =n−1Xj=0
Aj [b1γj1(t) + b2γj2(t) + · · ·+ b1γjp(t)]
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Controllability (7)The zero-state solution is
xzs(t) =n−1Xj=0
Aj [b1γj1(t) + b2γj2(t) + · · ·+ bpγjp(t)]
Suppose that the set of n× 1 vectors©b1,Ab1, · · · ,An−1b1
ªis linearly independent.
Then any state xzs(t) can be written as a linear combination ofthese n vectors, and the system is controllable
One way to state mathematically that the set of vectors is inde-pendent is to state that
rank£b1 Ab1 · · · An−1b1
¤= n
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Controllability (8)The zero-state solution is
xzs(t) =n−1Xj=0
Aj [b1γj1(t) + b2γj2(t) + · · ·+ bpγjp(t)]
If the set of vectors ©b1,Ab1, · · · ,An−1b1
ªis not linearly independent, then it has rank < n
However, there are still p− 1 controls remaining, and perhaps theadditional Ajbk vectors can be used to construct a linearly inde-pendent set of n vectors
One way to state mathematically that the set of vectors providesa set of n linearly independent vectors is
rank£B AB · · · An−1B
¤= n
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Controllability (9)The test for controllability, therefore, is to construct the controlla-bility matrix,
Mc =£B AB · · · An−1B
¤and determine whether it has rank n.
If rank B = p, the reduced controllability matrix can be used:
Mc =£B AB · · · An−pB
¤The controllability test for this case is also
rank Mc = n
What are the dimensions of these two controllability matrices?
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Controllability (10)Determine whether system
A =
∙1 00 3
¸, B =
∙01
¸is controllable.
Note that n = 2 and p = 1.
Mc = [B AB] =
∙01
03
¸The columns are linearly dependent and thus rank Mc = 1
The system is not controllable
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Controllability (11)Determine whether system
A =
∙1 00 3
¸, B =
∙11
¸is controllable.
Note that n = 2 and p = 1.
Mc = [B AB] =
∙11
13
¸The columns are linearly independent and thus rank Mc = 2
The system is controllable
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ObservabilityThe zero-input solution to x = Ax+Bu is
xzi(t) = eAtx(0)
The output equation is
yzi(t) = Cx = CeAtx(0)
Observability. Is there an initial condition, x(0) such thatyzi(t) = 0 for all time? If not, then the system is observable.
Keep in mind that x ∈ Rn, y ∈ Rm, A ∈ Rn×n, and C ∈ Rm×n
Also recall that the Cayley-Hamilton Theorem leads to
eAt =n−1Xj=0
αj(t)Aj
where the αj(t) terms are independent functions of time
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Linear Systems AnalysisLast time:
Modal Analysis
Controllability
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Linear System RecapStandard form for nonlinear system
x = f(x,u, t)
y = g(x,u, t)
Equilibrium motions: constant (x∗,u∗) such that
f(x∗,u∗, t) = 0
Linearization about (x∗,u∗) to obtain
x = Ax+Bu
y = Cx+Du
General solution for time-invariant system
x(t) = eAtx(0) + eAtZ t
0
e−AτBu(τ) dτ
= xzi(t) + xzs(t)
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Linear System With State and Output Feedback
Standard form for linear systems
x = Ax+Bu
y = Cx+Du
Two types of feedback: full-state, and output
u = −Kxx = [A−BK]x = Ax
u = −Kyx = [A−BKC]x = Ax
(Assuming no feedforward)
In both cases, the solution can be written as
x(t) = eAtx(0)
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An Aside on Linear AlgebraLinear systems analysis depends on many results from linear alge-bra, so a strong background in linear algebra is important
Linear algebra is much more than matrix multiplication, but muchof linear algebra involves how matrices multiply other matrices
An excellent reference is
Gilbert Strang, Linear Algebra and Its Applications
An n× n matrix A is nonsingular if and only if
F its rank is nF its rows are linearly independentF its columns are linearly independentF its determinant is non-zeroF none of its eigenvalues are zeroF the dimension of its nullspace is zero
All of these conditions are equivalent
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An Aside on Linear Algebra (2)Many of the matrices we see in linear systems analysis are notsquare
• The input matrix is usually (but not always) tall† (rows >columns)
• The output matrix is usually (but not always) short (rows <columns)
• The controllability matrix is always wide
• The observability matrix is always tall
The rank of a non-square matrix is the maximum of the number ofindependent rows or the number of independent columns
The rank cannot exceed the smallest dimension of the matrix
† These terms are not necessarily standard, but are suggestive
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Controllability RecapControllability depends on the two matrices A, B
(A, B) is controllable if the controllability matrix
Mc =£B AB · · · An−1B
¤has rank n
If rank B = p, the reduced controllability matrix can be used:
Mc =£B AB · · · An−pB
¤The controllability test for this case is also rankMc = n
If a system is controllable, then the eigenvalues of
A = A−BK
can be placed anywhere in the complex plane by appropriate choiceof K (provided that the complex eigenvalues come in c.c. pairs)
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Another Controllability Test
Another way to test for controllability is to apply the Popov-Hautus-Rosenbrock (PHR) test
rank [(λ1−A) B] = n
for all λ
Since λ1−A has rank n for all values of λ except for the eigenvaluesof A, the test only has to be applied at the eigenvalues
Using the controllability matrix test, rankMc = n, we form asingle n× np matrix and test its rank
Using the PHR test, we form nmatrices, each of which is n×(n+p),and test the rank of each of them
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Some Controllability Applications
Suppose rank B = n; then (A, B) is controllable because the firstn columns of the controllability matrix are linearly independent
Suppose p = 1, and B ∈ Rn is an eigenvector ofA; then the systemis uncontrollable
rank Mc = rank£B AB · · · An−pB
¤= rank
£B λB · · · λn−1B
¤= 1
Relate to the PHR Test
Suppose 1 < p < n, and the columns of B, bk ∈ Rn, k = 1, · · · , p,are all eigenvectors of A; then the system is uncontrollable
rank Mc = rank£B AB · · · An−pB
¤= rank
£B BΛs · · · B Λn−ps
¤= p
where Λs is the diagonal matrix of the eigenvalues correspondingto the columns of B
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Pole Placement
If (A, B) is controllable then the state-feedback closed-loop eigen-values (or poles) of
A = A−BKcan be arbitrarily placed in the complex plane by appropriate choiceof K, with the restriction that complex eigenvalues must be c.c.pairs
Suppose we want the closed-loop characteristic equation to be
p(λ) = λn + an−1λn−1 + · · ·+ a1λ+ a0
We can form the characteristic polynomial p(λ) and match its co-efficients with those of p(λ) to determine K
There are numerous methods for constructing K to match the co-efficients
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Pole Placement (2)Consider the linear system with
A =
∙1 00 2
¸and B =
∙1 00 1
¸Clearly the system is controllable, since the controllability matrix
Mc = [B AB] = [1 A] =
∙1 0 1 00 1 0 2
¸has rank n
Suppose we want u = −Kx, such that λ1,2 = (−1,−2)
Select the elements of K to place the eigenvalues of
A = A−BK =
∙1 00 2
¸−∙1 00 1
¸ ∙K11 K12
K21 K22
¸=
∙1−K11 −K12
−K21 2−K22
¸
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Pole Placement (3)The characteristic polynomial is
p(λ) = (λ− 1 +K11)(λ− 2 +K22)−K21K12
= λ2 + (K11 +K22 − 3)λ+ (K11 − 1)(K22 − 2)−K12K21
Evidently, for this example, we can choose K12 = K21 = 0, so that
p(λ) = λ2 + (K11 +K22 − 3)λ+ (K11 − 1)(K22 − 2)
The roots are
λ1,2 =1
2
h−(K11 +K22 − 3)±
p(K11 −K22 + 1)2
i=
1
2[−(K11 +K22 − 3)± (K11 −K22 + 1)]
= 1−K11, 2−K22
Thus K11 = 2,K22 = 4⇒ λ1,2 = (−1,−2)
Determine gains to place the eigenvalues at a specific complex con-jugate pair, λ1,2 = σ ± iω. May require non-zero K12 and K21
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Pole Placement (4)The characteristic polynomial is
p(λ) = λ2 + (K11 +K22 − 3)λ+ (K11 − 1)(K22 − 2)−K12K21
Determine gains to place the eigenvalues at a specific complex con-jugate pair, λ1,2 = σ ± iω
The desired characteristic polynomial is
p(λ) = (λ− σ − iω)(λ− σ + iω)= λ2 − 2σλ+ σ2 + ω2
For pole placement, we require
(K11 +K22 − 3) = −2σK11K22 −K12K21 − 2K11 −K22 + 2 = σ2 + ω2
Try K11 = K22 = K1 ⇒ K1 = (3− 2σ)/2K12K21 = 2− σ2 − ω2 +K2
1 − 3K1
• • •
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StabilizabilityStabilizability is a less stringent variation of controllability
(A, B) is stabilizable if the eigenvalues of
A = A−BK
can be placed in the left half of the complex plane by appropriatechoice of K
If a system is controllable, then it is stabilizable
The Popov-Hautus-Rosenbrock (PHR) test applies to stabilizabil-ity as well as to controllability
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Stabilizability (2)
(A, B) is stabilizable if λ(A = A−BK) can be placed in the lefthalf of the complex plane by appropriate choice of K
Stability ⇒ Stabilizability and Controllability ⇒ Stabilizability
The Popov-Hautus-Rosenbrock (PHR) test applies to stabilizabil-ity with slight modification
rank [(λ1−A) B] = n
for all λ with Re λ ≥ 0
Since λ1−A has rank n for all values of λ except for the eigenvaluesof A, the test only has to be applied at the eigenvalues, and onlyat the marginally stable and unstable eigenvalues
The essence of stabilizability is that all uncontrollable modes arestable and all unstable modes are controllable
If a system is unstabilizable, then the D&C folks are in trouble!
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ObservabilityThe zero-input solution to x = Ax+Bu is
xzi(t) = eAtx(0)
The output equation is
yzi(t) = Cx = CeAtx(0)
Observability. Is there an initial condition, x(0) such thatyzi(t) = 0 for all time? If not, then the system is observable.
Keep in mind that x ∈ Rn, y ∈ Rm, A ∈ Rn×n, and C ∈ Rm×n
Also recall that the Cayley-Hamilton Theorem leads to
eAt =n−1Xj=0
αj(t)Aj
where the αj(t) terms are independent functions of time
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Observability (2)Consider a linear system with
A =
∙1 00 3
¸, C =
£0 1
¤Since the states are completely decoupled, the solution to the statezero-input dynamics are
x1 = etx1(0) and x2 = e
3tx2(0)
The output dynamics are described by
y = Cx = x2 = e3tx2(0)
Clearly, if we choose any value for x1(0) and choose x2(0) = 0, theny = 0 for all time. Thus the system is unobservable, and clearlythe unobservability is caused by the lack of a connection betweenx1 and y.
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Observability (3)
We can obtain observability by adding another sensor, or connec-tion, between the state and the output:
A =
∙1 00 3
¸, C =
£1 1
¤The state zero-input dynamics are
x1 = etx1(0) and x2 = e
3tx2(0)
The output dynamics are described by
y = Cx = x1 + x2 = etx1(0) + e
3tx2(0)
Clearly, there are no choices for x1(0) and x2(0), such that y = 0for all time. Thus the system is observable.
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Observability (4)
Recall that the zero-input solution is xzi(t) = eAtx(0). Thus theoutput solution for zero-input dynamics can be written as
yzi = Cxzi(t)
= CeAtx(0)
Incorporating the Cayley-Hamilton summation for eAt, we canrewrite yzi as
yzi = Cn−1Xj=0
Ajαj(t)x(0)
= Cn−1Xj=0
Ajx(0)αj(t)
Recall that C ∈ Rm×n, and note that CA ∈ Rm×n also.
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Observability (5)
For there to be a non-zero initial condition x(0) such that yzi = 0,that initial condition would have to satisfy
CAjx(0) = 0 for each j = 0, · · · , n
This requirement can be written in matrix form as⎡⎢⎣ CA0
...CAn−1
⎤⎥⎦x(0) = 0, or Mox(0) = 0
If rank Mo = n, the system is observable
If rankMo < n, then the system is unobservable⇒ there are initialconditions such that the output is identically zero for all time
A PHR test for detectability is
rank
∙λ1−AC
¸= n for each eigenvalue
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Observability (6)
Consider the linear system:
A =
∙1 00 3
¸, C =
£0 1
¤The observability matrix is
Mo =
∙CCA
¸=
∙0 10 3
¸Clearly the rows of Mo are linearly dependent, and hence (A,C)is unobservable
If an additional sensor were added, so that C = [1 1], then thesystem would be observable
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Detectability
Detectability is related to observability in much the same way thatstabilizability is related to controllability
A system is detectable if the output observes all the unstable modes
In the concept of stabilizability, we are concerned with the eigen-values of the matrixA−BK, which arises due to a feedback controlof the form u = −Kx
A system is said to be detectable if an output-injection matrixL exists, such that the matrix A − LC is stable (i.e., has all itseigenvalues in the left-half plane)
A PHR test for detectability is
rank
∙λ1−AC
¸= n
for each unstable eigenvalue
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Duality
There is a duality between controllability and observability
The system (A,B) is controllable if and only if the system(AT ,BT ) is observable
Similarly, the system (A,B) is stabilizable if and only if (AT ,BT )is detectable
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Summary of C, O, S, D
Controllability means any statecan be reached in finite time
Tests:
rank Mc = n
rank [(λ1−A) B] = n
for each eigenvalue
Stabilizability means all eigenval-ues can be made stable with feed-back
Test:
rank [(λ1−A) B] = n
for each eigenvalue with Re λ ≥ 0
Observability means any statecan be detected in the output
Tests:
rank Mo = n
rank
∙λ1−AC
¸= n
for each eigenvalue
Detectability means all unstablemodes can be detected in the out-put
Test:
rank
∙λ1−A)C
¸= n
for each eigenvalue with Re λ ≥ 0
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Linear Systems Analysis
Last time:
Controllability
Stabilizability
Observability
Detectability
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Summary of C, O, S, D
Controllability means any statecan be reached in finite time
Tests:
rank Mc = n
rank [(λ1−A) B] = n
for each eigenvalue
Stabilizability means all eigenval-ues can be made stable with feed-back
Test:
rank [(λ1−A) B] = n
for each eigenvalue with Re λ ≥ 0
Observability means any statecan be detected in the output
Tests:
rank Mo = n
rank
∙λ1−AC
¸= n
for each eigenvalue
Detectability means all unstablemodes can be detected in the out-put
Test:
rank
∙λ1−A)C
¸= n
for each eigenvalue with Re λ ≥ 0
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… - ilities: Pop QuizFor each of the following systems, determine stability, controllabil-
ity, and observability, and explain your reasoning
A =
∙1 00 1
¸B =
∙1 00 1
¸C =
∙1 00 1
¸
A =
⎡⎣ 1 0 00 1 00 0 1
⎤⎦ B =
⎡⎣ 1 00 11 1
⎤⎦ C =
∙1 0 00 1 1
¸
A =
⎡⎣ −1 0 00 −2 00 0 −3
⎤⎦ B =
⎡⎣ 1 0 10 1 −11 1 0
⎤⎦ C =
∙1 0 00 1 1
¸
A =
⎡⎣ −5 0 01 −4 03 4 4
⎤⎦ B =
⎡⎣ 1 00 11 1
⎤⎦ C =
∙1 0 00 1 1
¸
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… - ilities: Pop Quiz (2)For each of the following systems, determine stability, controllabil-
ity, and observability, and explain your reasoning
A =
∙−1 3−3 −1
¸B =
∙10
¸C =
£1 0
¤
A =
⎡⎣ 1 0 00 −2 40 −4 −2
⎤⎦ B =
⎡⎣ 011
⎤⎦ C =£0 1 1
¤
A =
⎡⎣ −2 3 0−3 −2 00 0 −3
⎤⎦ B =
⎡⎣ 111
⎤⎦ C =£1 1 1
¤
A =
⎡⎣ −5 0 30 −4 0−3 0 −5
⎤⎦ B =
⎡⎣ 010
⎤⎦ C =£0 1 0
¤
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Linearization Example RevisitedConsider the motion of a spinning rigid body with a constant
“environmental” torque. The desired motion of spinning body is
ω∗ = [Ω1 Ω2 Ω3]. We want to linearize the equations of motion
about the desired motion.
Expressed in a principal frame, the environmental torque is ge.
The “control” torque, g∗, required to maintain the desired motion
is easily computed using Euler’s equations:
ω = −I−1ω×Iω + I−1ge + I−1g = f(x,u)0 = −I−1ω∗×Iω∗ + I−1ge + I−1g∗ = f(x∗,u∗)g∗ = ω∗×Iω∗ − ge
Given the desired motion, ω∗ and the environmental torque ge, we
can easily compute g∗, which is clearly constant
In this problem, x = ω, u = g, x∗ = ω∗, and u∗ = g∗
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Linearization Example Revisited (2)Rosetta stone: x = ω, u = g, x∗ = ω∗, and u∗ = g∗
Equations in scalar form:
ω1 =I2 − I3I1
ω2ω3 +ge1I1+g1I1= f1(x,u)
ω2 =I3 − I1I2
ω1ω3 +ge2I2+g2I2= f2(x,u)
ω3 =I1 − I2I3
ω1ω2 +ge3I3+g3I3= f3(x,u)
The matrix, ∂f∂x (x∗,u∗, t), is
∂f
∂x(x∗,u∗, t) =
⎡⎢⎣ 0 I2−I3I1
Ω3I2−I3I1
Ω2I3−I1I2
Ω3 0 I3−I1I2
Ω1I1−I2I3
Ω2I1−I2I3
Ω1 0
⎤⎥⎦ ≡ AClearly A depends only on the inertias and the desired steady
motion ω∗.
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Linearization Example Revisited (3)Rosetta stone: x = ω, u = g, x∗ = ω∗, and u∗ = g∗
Equations of motion:
ω1 =I2 − I3I1
ω2ω3 +ge1I1+g1I1= f1(x,u)
ω2 =I3 − I1I2
ω1ω3 +ge2I2+g2I2= f2(x,u)
ω3 =I1 − I2I3
ω1ω2 +ge3I3+g3I3= f3(x,u)
The matrix ∂f∂u (x
∗,u∗, t) is
∂f
∂u(x∗,u∗, t) =
⎡⎣ 1I1
0 0
0 1I2
0
0 0 1I3
⎤⎦ ≡ BAs with A, the matrix B is constant and depends only on the
inertias. Note that B = I−1
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Linearization Example Revisited (4)Thus, the linearized equations of motion are
˙δω = A δω +B δg or x = Ax+Bu
where
A =
⎡⎢⎣ 0 I2−I3I1
Ω3I2−I3I1
Ω2I3−I1I2
Ω3 0 I3−I1I2
Ω1I1−I2I3
Ω2I1−I2I3
Ω1 0
⎤⎥⎦ and B =
⎡⎣ 1I1
0 0
0 1I2
0
0 0 1I3
⎤⎦Note that δω = ω−ω∗, and δg = g−g∗. A typical control problemis to determine the control δg that will maintain the desired motion
in the presence of initial condition errors and other disturbances.
A recommended exercise is to choose values of I, ge, and ω∗, and
then compare the results of integrating the nonlinear differential
equations with the results of integrating the linear equations.
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Linearization Example Revisited (5)Use the numerical values from Homework 7:
ω∗ = [10 0 6]T ⇒ A =
⎡⎣ 0 −2 03 0 50 −2 0
⎤⎦B = diag[0.0333 0.0250 0.0200]
Clearly the input matrixB has rank n, so the system is controllable
What if the torque actuator about one of the axes were to fail?
Three possibilities:
B = B12 =
⎡⎣ 0.0333 00 0.02500 0
⎤⎦ , B13 =⎡⎣ 0.0333 0
0 00 0.0200
⎤⎦ ,B23 =
⎡⎣ 0 00.0250 0
0 0.0200
⎤⎦
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Linearization Example Revisited (6)Assuming no control torque about b3, we have
A =
⎡⎣ 0 −2 03 0 50 −2 0
⎤⎦B = B12 =
⎡⎣ 0.0333 00 0.02500 0
⎤⎦Controllability matrix:
Mc12 =
⎡⎣ 0.0333 0 0 −0.05000 0.0250 0.1000 00 0 0 −0.0500
⎤⎦Clearly, rank Mc12 = 3, so system is controllable with missing
input u3 (control torque about b3)
Note that we used the reduced dimension version of Mc
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Linearization Example Revisited (7)With no control torque capability about b2, we have
A =
⎡⎣ 0 −2 03 0 50 −2 0
⎤⎦B13 =
⎡⎣ 0.0333 00 00 0.0200
⎤⎦Controllability matrix:
Mc13 =
⎡⎣ 0.0333 0 0 00 0 0.1000 0.100000 0.0200 0 0
⎤⎦Clearly, rank Mc13 = 3, so system is controllable with missing
input u2 (control torque about b2)
Exercise: Determine the controllability for other failed actuator
cases
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Linearization Example Revisited (8)Block-diagonalization
A =
⎡⎣ 0 −2 03 0 50 −2 0
⎤⎦ ⇒ E =
⎡⎣ 0.8575 0.4082i −0.4082i0 0.8165 0.8165
−0.5145 0.4082i −0.4082i
⎤⎦
Eb =
⎡⎣ 0.8575 0 0.40820 0.8165 0
−0.5145 0 0.4082
⎤⎦ , Λb =⎡⎣ 0 0 00 0 40 −4 0
⎤⎦
eΛbt =
⎡⎣ e0t 0 00 cos 4t sin 4t0 − sin 4t cos 4t
⎤⎦ = R1(4t)
The matrix exponential, eΛt, turns out to be a rotation matrix
The real mode is marginally stable, as are the coupled oscillatory
modes
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Linearization Example Revisited (9)
-1
0
1-1 -0.8 -0.6 -0.4 -0.2 0 0.2 0.4 0.6 0.8 1
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1
b1b
b 3
Block-diagonalization
Eb =
⎡⎣ 0.8575 0 0.40820 0.8165 0
−0.5145 0 0.4082
⎤⎦The real mode is marginally stable, as are the coupled oscillatory
modes
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Linearization Example Revisited (10)To consider observability, we need to define an output vector
Suppose we have three rate gyros capable of measuring the rates
about the three principal body axes
y = ω = g(x,u, t) = g(x)
We want to linearize g(x) about x∗ to obtain the output matrix C
The matrix, C = ∂g∂x
¯x∗, is
∂g
∂x
¯x∗
= 1 ≡ C
Since C has rank n, the system is observable if all the sensors are
operable
What if a sensor fails?
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Linearization Example Revisited (11)Suppose two of three rate gyros fail; then C is simply one row of
the identity matrix
C ∈
⎧⎪⎨⎪⎩⎡⎣ 100
⎤⎦T ,⎡⎣ 010
⎤⎦T ,⎡⎣ 001
⎤⎦T⎫⎪⎬⎪⎭ , A =
⎡⎣ 0 −2 03 0 50 −2 0
⎤⎦The three observability matrices are
Mo ∈
⎧⎨⎩⎡⎣ 1 0 0
0 −2 0−6 0 −10
⎤⎦ ,⎡⎣ 0 1 03 0 50 −16 0
⎤⎦ ,⎡⎣ 0 0 1
0 −2 0−6 0 −10
⎤⎦⎫⎬⎭Clearly the first and third of these observability matrices both have
rank 3, but the second has rank 2
The system is unobservable with only a rate gyro on the b2 axis,
but is observable with a rate gyro on the first or third axes
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Linearization Example Revisited (12)Look more closely at the unobservable case
C = [0 1 0] , A =
⎡⎣ 0 −2 03 0 50 −2 0
⎤⎦The observability matrix is
Mo =
⎡⎣ 0 1 03 0 50 −16 0
⎤⎦The initial condition state that is unobservable is the vector x(0)
such that Mox(0) = 0
That is, x(0) ∈ N (Mo); in words, x(0) is in the nullspace of Mo
What initial state x(0) satisfies this condition?
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Linearization Example Revisited (13)We want to solve Mox(0) = 0
Mox(0) =
⎡⎣ 0 1 03 0 50 −16 0
⎤⎦⎡⎣ x1x2x3
⎤⎦ = 0
Carrying out the matrix multiplication, we obtain
x2 = 0⇒ x2 = 0
3x1 + 5x3 = 0⇒ x1 = −5x3/3−16x2 = 0⇒ x2 = 0
Clearly, any solution must lie along the line spanned by
x(0) =£−5/3 0 1]T
This line is the same as the eigenvector associated with the zero
real eigenvalue (check this claim); this mode is unobservable with
a 2-axis rate gyro
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Linearization Example Revisited (14)
Use the PHR test for detectability
rank
∙(λ1−A)
C
¸= n
for each unstable or marginally stable eigenvalue
rank
∙(01−A)
C
¸= n
rank
⎡⎢⎢⎣0 2 0−3 0 −50 2 00 1 0
⎤⎥⎥⎦ = 2
Therefore the system is undetectable, as well as unobservable
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Linear Systems Analysis
Last time:
Examples of Controllability,Stabilizability, Observability, and Detectability
This time:
PID (Proportional + Integral + Derivative) Control
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Way Back to Translational Motion
x1 = x
x2 = y
x3 = z
x4 = x
x5 = y
x6 = z
↓x ∈ R6
In general, the forces fx, fy, and fz could depend on xj and xj , aswell as on time t. The forces could also be nonlinear in the states.
x1 = x4
x2 = x5
x3 = x6
x4 = fx/m
x5 = fy/m
x6 = fz/m
x = f(x,u, t)
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Translational Linear System
Simple rearrangement of the equations of motion leads to the standard form:
Clearly this system is controllable and stabilizable (exercise)Also, the system is in a decoupled form that is common for mechanical systems
x =
⎡⎢⎢⎢⎢⎢⎢⎣0 0 0 1 0 00 0 0 0 1 00 0 0 0 0 10 0 0 0 0 00 0 0 0 0 00 0 0 0 0 0
⎤⎥⎥⎥⎥⎥⎥⎦x+⎡⎢⎢⎢⎢⎢⎢⎣0 0 00 0 00 0 01 0 00 1 00 0 1
⎤⎥⎥⎥⎥⎥⎥⎦u= Ax+Bu
What are the eigenvalues of A?
AOE 5204
Translational Linear System (2)
Looking back to the origin of these equations, recall that
x =
⎡⎢⎢⎢⎢⎢⎢⎣0 0 0 1 0 00 0 0 0 1 00 0 0 0 0 10 0 0 0 0 00 0 0 0 0 00 0 0 0 0 0
⎤⎥⎥⎥⎥⎥⎥⎦x+⎡⎢⎢⎢⎢⎢⎢⎣0 0 00 0 00 0 01 0 00 1 00 0 1
⎤⎥⎥⎥⎥⎥⎥⎦u= Ax+Bu
Consider using a full-state feedback that maintains this decoupling
x = fx/m(= u1), so
xj = uj
xj = xj+3 and xj+3 = uj
AOE 5204
Translational Linear System (3)We have the coupled pairs of equations:
xj = xj+3 and xj+3 = uj
If we let uj = −kpxj − kdxj+3, then
xj = xj+3 and xj+3 = −kpxj − kdxj+3xj + kdxj+3 + kpxj = 0
xj + kdxj + kpxj = 0
x+ kdx+ kpx = 0We can pick the gains kd and kp so that the eigenvalues have neg-ative real parts (detectability)
λ = σ ± iωp(λ) = λ2 − 2σλ+ σ2 + ω2
kd = −2σ and kp = σ2 + ω2
AOE 5204
Translational Linear System (4)
x+ kdx+ kpx = 0
Gain selection for pole placement
λ = σ ± iωp(λ) = λ2 − 2σλ+ σ2 + ω2
kd = −2σ and kp = σ2 + ω2
A standard form for this second-order system is
p(λ) = λ2 + 2ζωnλ+ ω2n
kd = 2ζωn and kp = ω2n
The damping ratio, ζ is usually chosen so that ζ ∈[0.5, 0.707], and the natural frequency ωn is the bandwidthof the system with PD control
AOE 5204
Translational Linear System (5)
Gain selection in terms of ζ andωn:
kd = 2ζωn and kp = ω2n
Solution to ODE:
x(t) = e−ζωnt (c1 cosωdt+ c2 sinωdt)
where ωd = ωnp1− ζ2
The damping ratio, ζ is usuallychosen so that ζ ∈ [0.5, 0.707],and the natural frequency ωn isthe bandwidth of the system withPD control
Re λ
Im λ
×sin−1 ζ
ωn
×
ωd
σ
AOE 5204
Translational Linear System (6)
Suppose the second order systemwith PD control is subject to aunit step disturbance:
x+ kdx+ kpx = ustep
where
ustep = 0 ∀ t ≤ 0ustep = 1 ∀ t > 0
What happens as t→∞?
0
0.1
0.2
0.3
0.4
0.5
To: O
ut(1
)
0 0.5 1 1.5 2 2.5 3 3.5 40
0.05
0.1
0.15
0.2
0.25
0.3
0.35
0.4
To:
Out
(2)
S tep Response
Time (sec)
Am
plitu
de
Answer: The output (x) does not stabilize to theorigin. Rather, x(∞)− > 1/kp
AOE 5204
Translational Linear System (7)
The differential equation be-comes
x+ kdx+ kpx = ustep + uI
Differentiate once to get
xiii + kdx+ kpx+ kIx = 0
The roots of the characteristicequation include the two PDeigenvalues and an additionalpole at −kI/ω2nThe term kI/ω
2n is typically
denoted 1/T , where T is theintegral or reset time
How can we stabilize in pres-ence of step disturbance:
x+ kdx+ kpx = ustep ?
We have feedback controlforces that are proportionalto the error (kp) and propor-tional to the derivative of theerror (kd).
Introduce a feedback controlforce that is proportional tothe integral of the error (kI)
uI = −kIZ t
t0
x(τ ) dτ
AOE 5204
PID Control
PID Control includes threeterms: proportional, deriva-tive, and integral:
up = −kpxud = −kdx
uI = kI
Z t
t0
x(τ) dτ
This type of control makesthe output robust to constantdisturbances, but also makesthe system less stable (or lessdamped)
Typically, PID control is writ-ten as
u = −kx− kTDx
− kTI
Z t
t0
x(τ) dτ
There are several ways to tunethe three parameters appear-ing in the PID control