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TRANSCRIPT
1
Chapter 1.0: Introduction
1.1 Application of research
Power factor is the ratio between the KW and the KVA drawn by an electrical load
where the KW is the actual load power and the KVA is the apparent load power. It is a
measure of how effectively the current is being converted into useful work output and
more particularly is a good indicator of the effect of the load current on the efficiency of
the supply system.
When an electric load has a PF. lower than 1, the apparent power delivered to the load
is greater than the real power that the load consumes. Only the real power is capable of
doing work, but the apparent power determines the amount of current that flows into the
load, for a given load voltage.
All current will causes losses in the supply and distribution system. A load with a power
factor of 1.0 provides most efficient loading of the supply and a load with a power
factor of 0.5 will result in much higher losses in the supply system.
A poor power factor can be the result of a significant phase difference between the
voltage and current at the load terminals. Poor load current phase angle is generally the
result of an inductive load such as an induction motor, power transformer, lighting
ballasts, welder or induction furnace.
2
1.2 Objective of this thesis
An improved power factor AC output is the main target of this project. This project
focuses on the design and implementation of power factor correction using PIC micro-
controller chip, determine the power factor of the loaded power system, generate proper
action to calculate and to pin point adequate capacitor to redeem appropriate power lost
under the project design using MikroC program and finally test or simulate the design
with PIC chip stand individual without interface of personal computer.
1.3 Structure of thesis
This thesis is divided into main six chapters that are literature background, role of
capacitor, different approach of power factor correction, System Design,
implementation & results, future direction and conclusion. The literature background
(chapter 2) discuss about the fundamentals knowledge of power factor and its
applications. While the role of capacitor (chapter 3) is one main component that used to
correct power factor, its relation with power factor and application background are
mainly explain in this chapter.
In meantime, few types of power factor correction methodologies under difference
circumstances are outlined for the present power factor correction methods used in
various approaches (chapter 4). Then next chapter (chapter 5) is the system design of
this project; this section explains the process of how the overall design works using PIC
micro-controller chip. After the explanation of the working principle of the system
design, the testing results and ways of implementation will be analyzed and discussed in
3
chapter 6. Finally, in chapter 7, this thesis ends with conclusion as well as
recommendations for future research.
4
Chapter 2.0: Literature Background
2.1 Power Relation with power factor
It is known that reactive loads such as inductors and capacitors dissipate zero power, yet
the fact that they drop voltage and draw current gives the deceptive impression that they
actually do dissipate power. This "phantom power" is called reactive power, and it is
measured in a unit called Volt-Amps-Reactive (VAR), rather than watts. The
mathematical symbol for reactive power is the capital letter Q. The actual amount of
power being used, or dissipated, in a circuit is called true power, and it is measured in
watts (symbolized by the capital letter P). The combination of reactive power and true
power is called apparent power, and it is the product of a circuit's voltage and current,
without reference to phase angle. Apparent power is measured in the unit of Volt-Amps
(VA) and is symbolized by the capital letter S.
There are several power equations relating the three types of power to resistance,
reactance, and impedance (all using scalar quantities), E here refers as voltage in single-
phase:
θcos×= EIP (real part)
θsin×= EIQ (imaginary part)
jQPQPEIS +=+== 22
⎥⎦
⎤⎢⎣
⎡⎟⎠⎞
⎜⎝⎛==
×== −
PQ
EIEI
SPPF 1tancoscoscos θθ
5
Where, P = Real Power (unit in Watt),
Q = Reactive Power (unit in VAR) and
S = Apparent power (unit in VA)
PF = power factor
For three-phase system, the power equation mostly measure in kilo-unit or Mega-unit,
where ph denotes as phase and L denotes as line. Before attempting to determine the
power factor in three-phase system, there are mainly two ways of loads connection
appears in three-phase power system: wye (or star) connection and delta connection,
that needs to be aware of. (H. Saadat, 1999)
In wye-connection load, (Y)
phL
PhL
IIVV
=
°∠= 303
As for in delta connection, (∆)
°−∠=
=
303 phL
phL
II
VV
And the relationship of wye and delta connection in impedance is as follow.
3∆=
ZZY
6
Thus the power relationship would be
( )∑=
=
×=Nj
jpjph pj
IVN
P1
*3 or ( )∑=
=
×=Nj
jLjL Lj
IVN
P1
*3 with cos θ;
( )∑=
=N
jpjpj IV
NQ
1
*3 or ( )∑ ∗= pjLj IVN
Q 3 with sin θ;
( ) ( )2
1
1
22
1
1
2 113 ⎥⎦
⎤⎢⎣
⎡×⎥
⎦
⎤⎢⎣
⎡×= ∑∑
==
N
jpj
N
jpj I
NV
NS or
( ) ( )2
1
1
22
1
1
2 113 ⎥⎦
⎤⎢⎣
⎡×⎥
⎦
⎤⎢⎣
⎡×= ∑∑
==
N
jpj
N
jLj I
NV
NS
⎥⎦
⎤⎢⎣
⎡==== −
)()(tancoscos 1
kWPkVARQ
kVAkW
SPPF θ
The power equations shown in previous section are in balanced condition. Apparently, a
pure balanced condition is rarely existed but mostly able to draw near to acceptable
range. One of the main reason the results to unbalance are earthed system elements that
leads to current flowing in earthed neutral and earth ground itself is a gigantic
grounding terminal that easily create faulty for electronic circuit if without proper
prevention and taking safety caution.
The equations for unbalanced condition use a, b and c for different loads notation; in
other words, instantaneous power is formed by summation of instantaneous values of
Va, Vb, and Vc multiply with of instantaneous values of current Ia, Ib and Ic.
ccbbaa IVIVIVP ++=
Where, 0=++ cba III
7
Therefore the power expression would be,
Using ( )baC III +−=
( )bacbbaa IIVIVIVP +++=
Or ( ) ( ) bcbaca IVVIVVP ×−+×−=
On using caac VVV −= and cbbc VVV −=
bbcaac IVIVP +=
Therefore with respect of time-series, the expression of real power and reactive power is
as shown below.
( )⎭⎬⎫
⎩⎨⎧
+×= ∑=
=
Nj
jbcjacj bjaj
IVIVN
P1
**1Re
( )⎭⎬⎫
⎩⎨⎧
+×= ∑=
=
∗∗Nj
jbjbcjajacj IVIV
NQ
1
1Im
The apparent power and the power factor calculation would be the same as balanced
condition.
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2.2 Why power factor correction
As slight explained in the introduction, the existing of reactive power does not included
in the electric bill yet this probably causes dissipation power lost at the load, which
results to an increment of electricity bill charge. Penalty charge is just one of the feature
concerned mostly by electricity user, however there are more other problem occurs if
power factor is low.
• Penalty charge in electric bill;
• Extra losses in feeder cables;
• Significant voltage drop
• reduction of effective capacity of cables
• Reduction in power available at the transformer
• Significant voltage drop at the secondary of the transformer
• Significant losses in transformer
2.2.1 Reasons cause lower power factor
All current will causes losses in the supply and distribution system. A load with a power
factor of 1.0 results in the most efficient loading of the supply and a load with a power
factor of 0.5 will result in much higher losses in the supply system.
A poor power factor can be the result of either a significant phase difference between
the voltage and current at the load terminals, or it can be due to a high harmonic content
or distorted/discontinuous current waveform.
System that has inductors like motors and electronic devices will produce inductive
reactance and thus generate lagging reactive power. The main reason is the current
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flows within power system. No matter how a power system designed, current will
surely causes loss in both supply and distributed loads. Load with power factor of 1.0
has best efficient of power usage upon the load itself and this can only appear in pure
resistive circuit. A poor power factor appears due to the significant phase difference
between voltages and currents at load terminals are large, which thus gives power factor
value lower than unity (=1).
Unfortunately this is not the only reason that power factor drop. High harmonic or
distorted/discontinuous current waveform will also cause low power factor; however
this is not mainly designed but it will be discussed in chapter 4, which about various
approaches attempt to different kind of power factor failures. System that contains
motor, power transformer, lighting ballasts, welder or induction furnace are the main
reasons that result phase shift in sinusoidal load current. While system that possess
rectifier, variable speed drive, switched mode power supply, discharge lighting or other
electronic load creates harmonics and have high possibility cause current signal to be
distorted or discreet. Simple capacitor bank cannot fix the such problem, a change in
equipment design or expensive harmonic filters are needed to perform further
improvement.
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2.3 Power factor correction Process
This can be discussed with an example [quote]. Since single-phase is considered one of
the phase in three-phase system when connected in wye-connection, hence the
following calculation procedures would use single-phase scene as base.
Aj
jI
AI
8420100200
02100
0200
2
1
−=+
°∠=
°∠=°∠
=
( )
var1600800)84(0200
var0400020200
22
11
jWjVIS
jWjVIS
+=+×°∠==
+=−×°∠==∗
∗
Total apparent power and current are
A
VSI
VAjjQPS
°−∠=°∠
°−∠==
°∠=+=+=
∗
∗
13.53100200
13.53200013.53200016001200
The power factor vat the source is
( ) 6.013.53cos =°=PF lagging
The main target is to get nearer power factor to unity hence the following action being
done.
I IC
I1 I2
100Ω
10Ω
j20Ω
200V C
11
Total real power remains the same, P = 1200 W with new power factor choose to be
cross to unity, say 0.95 lagging
°== − 19.18)95.0(cos 1newθ
( ) var4.39419.18tan1200tan =°×== newnew PQ θ
var6.12054.3941600 =−=CQ
( )Ω−=== ∗ 18.33
6.1205200 22
jjS
VZ
CC
FC µπ
93.9518.33502
1=
××=
Since there is no exactly 95.93µF, a near capacitor value like 90µF can be chosen with
a slight lower of PF value.
This example pre-determined a desired power factor of 0.95 so getting a nearest PF can
also choose capacitor value of 100µF with PF value is approximately 0.96 (or 96%) but
if a system designed to get as close to unity, it is better to pick a lower capacitor value
to avoid excessive of leading current flow into the line bus. Since unity power factor
gives rise to the greatest utilization of the plant. Electric utilities measure reactive power
used by high demand customers and charge higher rates accordingly.
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Chapter 3.0: Role of Capacitor
Frequency is standardized at constant 50 Hz, or 60 Hz in other countries; power factor
correction is veiled as a solution to such fixed network frequency, the only key solution
is by addition of capacitor in shunt to the load. Capacitors are commonly used within a
lot of power system, especially electronic constructed circuitry. Though common it is, it
is consequently least understood by majority as one most beneficial component for
power system.
• Release of system capacity
• Reduction of kVAR generation requirements
• Reduction of system loss
• Regulation or improvement in voltage
These benefits require only small amount of investment and maintenance compare to a
lot of power system components. Budgeting expenses itself already a solid reason for
why capacitors are most welcome in many power system.
In three-phase power system, capacitors normally installed within an isolating non-
conductor metal box, which called capacitor bank; they are either fixed or switched.
Fixed banks are connected permanently to the primary conductors through fused
switches. Switched banks are tied to the primary system through automated switches,
allowing them to be put on line and taken off line as needed. Distribution power system
usually connects capacitor in parallel (also called shunt) rather connecting in series.
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The function of shunt power capacitor is to provide leading (capacitive) kVARs to an
electrical system when and where needed. Lagging (inductive) kVARs appear when
there are inductors (coils) exist within electrical (e.g. motor) or electronic (personal
computer) equipments, as the amount grows, the increment of inductive kVARs will
increase as well, thus the demand of capacitive kVARs to compensate is pretty much
required in order to reduce unnecessary lost. (TVPPA, Distribution Design Guideline)
The actual capacitor in farads of a capacitor bank can be calculated using the following
equation:
22 RVfVARC×
=π
(3-1)
where, VAR = capacitor unit VAR rating
C = capacitor (farads)
f = frequency (cycles/second)
VR = capacitor unit rated voltage
3.1 Relationship of capacitor with power factor
Capacitor is the main component that supplies capacitive reactance, which is negative
reactive power. Since the power factor is the ratio of real power and apparent power,
where apparent power has the relation with reactive power and real power as shown in
the power triangle in figure 3-1. As majority power system has inductive loads thus
normally only lagging power factor occurs hence capacitors are used to compensate by
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producing leading current to the load to reduce the lagging current, thereby shrink the
phase angle distance between the real power and apparent power.
Figure 3-1: Power triangle
Table 3-1 list a number of common loads appears in general industrial systems and their
typical power factor.
Load Typical Power Factor Incandescent lamps 1.0 Florescent lamps 0.95 – 0.97 Synchronous motors 1.0 to 0.80 leading Squirrel cage motors High speed 0.75 – 0.90 Low speed 0.85 –0.92 Wound rotor 0.80 – 0.90 Induction motors Fractional HP 0.55 – 0.75 1 – 10 HP 0.75 – 0.85 Arc furnace 0.65 – 0.70 Power Converter 0.50 – 0.90
Table 3-1: Typical power factors of end use equipment
3.1.1 Connection Type
In general, power capacitors shall be wye-connected on the three-phase distribution
feeder. Grounding the neutral is essential for the fuses to operate in case of any event of
capacitor fault. For a small ungrounded wye-connected capacitor bank, faulty capacitor
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would not blow the fuse to isolate faulty capacitor. Any event of this could lead to an
explosion to the capacitor bank.
However, Isolating the neutral of the wye of a capacitor bank has the advantage of
reducing harmonics. (Quote) The method can only be an alternative when grounding the
neutral would cause operating difficulty for a particular installation. In case of
insulation failure inside the unit, phase-to-ground fault can still occurs to an ungrounded
wye capacitor bank even with its enclosure properly grounded.
The most effective solution is to insert reactors in series with each capacitor group
connected between the phase wire and the neutral of a three-phase bank. This method is
used to mitigate any resonant circuit, while reduction of induction triple harmonic
frequency current can be made.
3.2 Determine Size of Capacitor Banks
Standard capacitor sizes are 50, 100, 150, 200, 300 and 400 kVAR. Since three-phase
installations are pretty much the same as single phase installation, which single-phase is
just one of the phase among three phase connection. Of course, the formula for both
phases will be different. Since capacitors can be connected more than one per phase in
order to increase the bank size, it is recommended to select two or at most three
capacitor unit sizes to avoid stocking the sizes. (TVPPA Group, Distribution design
Guidelines)
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ILAG
Time
Loss reduction = 0%
ILAG MAX
Rective current without capacitor
Loss reduction = 89%
ILAG MAX
Icap
Cap off at ILead Max = (1/3)Icap
Cap off at ILead Max = (2/3)Icap
Reactive current with capacitor (Maximum loss reduction)
Figure 3-2: Reactive current with capacitor (maximum loss reduction)
(TVPPA, Distribute design guidelines)
How much amount of capacitance to install within a bank is considered sufficient? In a
fixed capacitor installation, one should at first determine desired power factor value
before attempting to design one. By installing fixed capacitor can approximately
improve the power factor around 94% to 96%. Higher power factor may only be
acquired with switched capacitor banks.
When using switched capacitor to correct the power factor of a circuit, the switch
control is set to close the bank onto the line when the load kVARs equal two-thirds of
the bank’s rated kVAR. This scheme is tend to reduce loss by driving the line leading
17
with first turn on before it is turn off, this is referred as the “two-thirds rule.” Taking a
daily load cycle as shown in figure 3-2 as example.
Compare with fixed capacitor bank, switching capacitor bank is generally more
expensive thus it is essential to take accounting of the cost of installation so that its time
value worth for the investment.
3.3 Possible Problems Occur in Capacitor Bank
Despite the benefits provided by capacitor bank, there are several possible undesired
events occur in the process of using capacitor bank, which mostly happen when
capacitor performs charge and discharge process.
3.3.1 Switching Counter Strike
In three-phase bank of capacitor connected in wye with neutral grounded, the initial
voltage is practically zero since capacitor on load side of the switch holds the same
instantaneous voltage as existed on the supply side. Since capacitive current leads
voltage by 90°, voltage of capacitor peak and circuit at same value, voltage across the
switch contacts tend to be twice the peak value compare with the fundamental on half
cycle period which capacitor at its moment of full charged and the supply voltage in
meantime reached its peak of opposite value, as shown in figure
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Figure 3-3: Voltage across switch contacts during the first half cycle.
(TVPPA, Distribution Design Circuit)
For the moment across switch gap, the capacitor voltage will overshoot when attempted
change in voltage in order voltage across the capacitor interrupted leaving three times
its steady state value. Same behavior happens in first current zero as its arc again may
be interrupted leaving three times normal peak voltage on the capacitor. After one-half
cycle, another four times will appear at switch contact as shown in figure 3-4. These
two time periods of overshoot behaviors are the counter striking back to the circuit,
therefore sufficiently separation between contacts or else a counter strike across switch
gaps will occurs. Proper steps like choice of switching devices and component like
diode that only allow one way current flow to protect controlling circuit from counter
striking.
T1T0 T2 T3
2EC across switch
contacts
Capacitor Voltage To = Beginning of switching opening; T1 = First current zero; T2 = ½ cycle after first current zero; T3 = switch completely opened.
Voltage
Current
19
Figure 3-4: A strike caused by difference of capacitor voltage and line voltage.
(TVPPA, Distribution Design Guideline)
3.3.2 Harmonic Problem
Increment of power electronic devices had drawn attention of high concern with
harmonics level. Capacitors individual does not cause harmonic current; however, the
rising of frequency when capacitive impedance drop will results harmonics generation
and affecting the magnitude of voltages and currents within the buses, especially when
capacitor banks connected in grounded wye to earth.
It is advised that capacitor bank should be placed at somewhere with proper distance
based on pre-defined desire power factor, rated voltage, etc with the actual system.
Another method is use ungrounded wye connection, this will prevent harmonic
4 EC switch contacts after counter strike
Bus voltage
Voltage
C
Counter Strike
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produces but careful study of capacitor switches to prevent switching counter attack and
capacitor bank short circuit protection.
For small capacitor bank, connecting in delta formation also have the same effect but
make sure proper discharge function must be installed, like connecting resistors in
between line-to-line of the three-phase delta-connected capacitor; nevertheless, the
switching effect problem must still be cautioned.
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Chapter 4.0: Different Approaches of PFC
In the precious chapter, the method that directly used of capacitor to correct power
factor as discussed in section 2.3 only applicable when current waveform was nearly
perfect sine wave. There are nowadays many power systems contains complicated
power electronic components or drives systems, such as converters, inverters, variable
drives system, etc; these types of power systems would mostly distort current waveform
or produce discreet signal output. Therefore this chapter will briefly converse about
different type of approaches apply in power factor correction for various type of
electrical power systems.
This chapter mainly categorized into two major types of power factor collecting circuit
methodologies. The first category is called the passive power factor correction, which
usually more reliable, inexpensive and typically improves power factor value up to a
maximum of 80%; while the second category that generally more effective and able to
achieve over 95% of corrected power factor is called the active power factor correction
method, this types generally integrated with switch-mode power supply. (Power factor,
LM Photonics Ltd.)
4.1 Passive PFC
Passive power factor correction is quite common in many distribution power system, it
mainly use capacitive filter (or fixed capacitors) to generate leading reactive current to
correct poor power factor. The initial setting of the AC input voltage will determine the
22
amount of capacitive filter needed for the power system and all this being done
manually. This type of power factor correction is practically sufficient enough for
system that had planned not to be altered much at the input for long time; and certainly
it is comparatively cheap compare to active PFC, which would be discussed in section
4.2. Generally, the desired power factor value is pre-calculated and selects sufficient
capacitors to perform constant power factor correction. However, passive PFC may be
affected when environmental vibration occurs and it cannot fully utilise the energy
potential of the AC line. [1]
Certainly that passive PFC can only apply to general power system that acquires pure
sinusoidal voltage and current waveforms. For sophisticate power electronic systems
that easily affected by harmonic distortion, active PFC is a better choice for long term
investment.
4.2 Active PFC
Active power factor is more preferable since it capable in providing more efficient
power frequency by diminishing total harmonics and phase different in between input
current and input voltage. Majority of active power factor are circuits built integrate
with the switched mode power supply, using IC and other active elements like diode
and FET. Follow ahead of this sector are introduction of few types of active PFC.
The effect of harmonic distortion makes many advanced systems suffer with lower
power factor as by normal mean of power factor correction method cannot solve the
problem as current might not even have the shape of sine wave. A diagram in figure 4-1
23
shows what exactly happen to the distorted current compares with perfect sinusoidal
current waveform.
Figure 4-1: Voltage and current waveform behavior
I represents the fundamental current out of phase in sine wave in an angle difference, θ;
while I’ is the actual current waveform. In other word, passive PFC circuit only capable
to correct poor power factor when only I exist in the power system, but if instead I’
occur then the corrected power factor using passive PFC circuit would not be precise;
losses and weak performance still remain yet power factor might read as 0.9 but instead
it is actually lower to 0.6. As a result, active PFC is developed to overcome the above
circumstances.
4.2.1 Basic converter topology switch mode PFC
The following are six types of single-phase switching converter-based active power
factor correction circuits: Buck, boost, buck-boost, flyback, cuk and sepic.
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Figure 4-2: Converter types of PFC
(a) Buck, (b) Boost, (c) Buck-Boost, (d) Flyback, (e) Cuk and (f) Sepic
The buck converter type circuit in figure 4-2(a) able to take in discontinuous current and
supply continuous current. Despite it can supply lower voltage from the input voltage, it
cannot convert a higher voltage when needed; harmonic current distortion would occur
if input voltage is lower than certain range, plus the input current intake is
discontinuous, thus it does not suit to AC/DC converting system. As for the boost
converter circuit in figure 4-2 (b), the working principle is just the opposite of buck
converter PFC circuit. The intake current is continuous while the output is
discontinuous. Since the input voltage can directly control the switching, it is practically
able to obtain near unity power factor. Of course, it can only produce constantly high
25
voltage output. This type of PFC converter is the most popular topology used in switch
mode power factor collection circuit.
Next is the buck-boost converter topology in figure 4-2 (c). This type of converter
allows stepping up or down voltage input, the polarity is opposite compare with the
output voltage. Unfortunately the current supply to the circuit is discontinuous and peak
current tend to bypass switching component, thus create harmonic, a harmonic filter is
needed. The fly-back type isolates both input and output terminal and the circuit
operation works under discreet current manner to control the switching hence normally
when used for system that aim for higher power factor and low harmonic distortion
would tend to install filters to increase switching speed, yet may reduce the overall
efficiency and require additional EMI filter. This type of switch mode PFC is suitable
for high voltage but low power system, which generally used for assisting high power
converter.
As shown in figure 4-2 (e), the circuit structure of cuk topology pretty much the same
behaviour as buck-boost topology, only lesser components. The sepic is the simplified
version of buck-boost with two switching control and continuous input current that able
to correct power factor to near unity. Each of these six types of converters PFC circuits
has their own advantages and disadvantages, taking concern of discontinuous
conduction mode (DCM), the distinguish power factor correction performance are
outlined in table 4-1.
26
Basic Converters Input current waveform Effect of DCM power factor correction
Buck
Less effective
Boost
Good
Buck-Boost
Best
Fly-back
Best
Cuk and Sepic
Less effective
Table 4-1: Converter base switch-mode PFC circuits attributes
27
4.2.2 Dither, Half-Bridge and Full-Bridge type PFC circuits
Figure 4-3: Dual and more switching mode PFC circuits
(a) Dither circuit, (b) half-bridge circuit, and (c) full-bridge circuit.
The converter based switch mode PFC in section 4.2.1 can only allow one way flow and
low power system. This section will introduce three types of bidirectional control
switch mode PFC circuits, there are dither, half-bridge and full bridge circuits.
The dither topology shown in figure 4-3 (a) uses two switches to perform switching
operation, where S1 and D1 take charge in correcting positive half cycle of waveform,
while S2 and D2 working on the negative portion. Such circuit commonly placed before
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an electronic circuit for power factor improvement. The only problem exists in this
circuit is when voltage crossing zero, harmonic appears as the voltage difference
between the switching are too small thus results the current waveform cannot maintain
perfect sine wave at that particular portion.
The half-bridge circuit in figure 4-3 (b) also has two control switches with two
capacitors. Similar with the dither topology, S1 and D1 perform correction at the
positive half cycle while S2 and D2 responsible for the negative half. Due to this circuit
has only one semiconductor component, the amount of power lost is relatively small,
plus it has two supportive capacitors so it is very suitable for supplying high voltage and
bidirectional source design.
As for the full-bridge circuit in figure 4-3 (c), there are altogether four control switches
that allows complete control of the waveform with the same working principle as the
previous two circuits. S2, S3 working as D1, D4 for positive half cycle, and S1, S4 as D2,
D3 for negative half cycle. Since the full-bridge topology constructs with extra two
control switches hence it is naturally cost higher and complicated to build one but in
return, its ability to reduce total harmonic distortion down to the lowest extend and no
distorted current appears at zero crossing like what happen in the dither topology. This
is because in full-bridge topology has wider potential difference at zero-crossing hence
the current able to catch up with the proper sine wave shaping.
A comparison summary of the nine switch-modes is displayed in table 4-2.
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Converter Type Circuit Structures Characteristic Single switch mode Buck
Boost Buck-boost
Fly-back Cuk
Sepic
1. Easy control 2. Current flow only one way 3. Only suitable with low power system
Double switches mode
Dither boost Half-bridge
1. Power can be transferred bidirectional however Capacitive Voltage might appear unstable.
2. Suitable for medium and low power supply system
Four switching mode
Full-bridge 1. Complicated, high cost 2. Dual direction transfer 3. Typically suits for high power
transmission. Table 4-2: Summary of nine converters PFC circuits general characteristics.
4.2.3 PFC control in switch-mode converter topology
Though out the basic analysis of power converter topology type of PFC, it is well
understood that the converter circuit such as boost converter, which able to perform
conversion upon continuous current, has less electromagnetic interference, voltage
control switching so that waveform able to maintain according to the original sinusoidal
waveform, hence its power factor manage to reach near unity. Typically boost converter
type PFC is quite famous with its simple design construction and far superior in
correcting power factor for small voltage. Therefore using boost converter topology as
base for explanation for the type of PFC control undertaking in general power converter
based PFC circuits.
The main target to carry out power factor correction is divided into continuous
conduction mode (CCM) and discontinuous conduction mode (DCM). If a design able
to control both modes simultaneously, the efficiency might boost to certain extreme.
However DCM is not commonly applied to many systems and meanwhile CCM has the
30
following benefits that determine its superiority compared to DCM, which thus DCM is
normally omitted when designing one:
1. Able to obtain higher power factor value and lower EMI.
2. Able to use smaller output capacitor and high power density.
3. Also able to be used in high power system.
31
Chapter 5.0: System Design and Structure
5.1 Main equipment Description
Programmable Interface Circuit chip, short form named PIC chip; it is the Microchip
Technologies’ series of micro controller. In other word, PIC is a type inexpensive
single-chip computer that confines integrated circuit within it. Basically, it looks like a
standard personal computer, which contains a CPU (central processing unit), RAM
(Random-access memory), ROM (Read-only memory), I/O (input/output) lines, serial
and parallel ports, timer, internal oscillator, and even built-in peripherals such as A/D
(analogue-to-digital) and D/A (Digital-to-analogue) converters, sample/holder (S/H);
more advanced features can be found in the latest series of PIC chip. The PIC used in
this project is PIC16F777, which contains comparator function.
Such chip is programmed via a PIC programmer board (K8048) interfaces with personal
computer using MikroC programmer and WinPIC programmer both freeware. The
MikroC programming software is a programming software recognized by Microchip
Cooperate.
32
Figure 5-2: K8048 Programmer Board
5.2 Circuit Designs
The design aims to monitor phase angle continuously and in the event of phase angle
deviation, a correction action is initialized to compensate for this difference by
continuous changing variable capacitors value via switching process. The overall
system requires the only one PIC chip, few power electronic components and a bank of
capacitors. Figure 5-2 shows the hardware block diagram layout of the overall system.
33
Figure 5-2: Overview of design system
5.2.1 Sensors
The alternative voltage and current signals are both sensed and scared down using
sensors, while the current is converted into an equivalent voltage representation. The
sensing devices used to detect the voltage signal are a LV 25-P and LA 55-P. LV 25-P
is a type of voltage transducer that able to read both DC and AC signal by converting
the captured signal into smaller scale with ratio of 2500:1000; while LA 55-P is a
current transducer that scares down input signal with ratio of 1:1000. These two devices
can only be used if ± 12V…15V is supplied. The devices appearances are displayed in
figure 5-3.
It is essential to take caution that PIC chip can only take in certain range of input
voltage, either the range of 0 to 5V with current limiting to 20mA, or higher range of
voltage reading with condition that current limited within range of micro (µ) unit. In
other word, the total power dissipated within the PIC chip must not exceed 1W. The
power dissipation is calculated using the following formula.
Main C
omputation Procedure
Sensors Determine phase angle and command proper action for correction
Zero-Crossing Detector
V I
Switching D
rivers
……
…
Capacitor B
ank
Power Factor
improved
AD
C
S/H system
PIC16F777 Chip
34
( ) ( )[ ] ( )∑∑∑ ×+×−+−×= OLOLOHOHDDOHDDDDdiss IVIVVIIVP
Figure 5-3: Voltage and Current Sensors
5.2.2 Zero crossing detector
The sensed signals transfer into zero-crossing detecting procedure. Originally, zero
crossing can be detected using a specific design circuit; a simple zero-crossing detector
circuit sample is shown in figure 5-4. However such design cannot apply when input
voltage is too low, the output pulses tend to be distorted; a simulated result shows in
figure 5-5 and figure 5-6 that describe the drawback of this circuit. This is merely
simulation, the actual output also being tested and discovered that the output waveform
was even distorted.
Figure 5-4: Typical sample of zero-crossing detector circuit
35
When input voltage = 110V.
Figure 5-5: Output pulses when input AC supply voltage high enough
When input voltage = 5V
Figure 5-6: Output pulses when AC supply voltage is low
36
Figure 5-7: PIC chip interface zero-crossing detector
The approached were constructed into actual circuit in figure B-4 of appendix B and
proven the circuit are relatively hard to work fine practically. Such problem can be
solved directly by inserting the input voltage and current signal into the PIC chip with
proper component used to prevent damage to the microchip.
It is mentioned that as far as PIC chip is within 1W power dissipation, high alternating
input voltage are acceptable by the chip input pins. For that, a high external resistor
must be placed before the pin in order to ensure very low current supply into it. A
typical input AC voltage, 50 Hz, sine wave will definitely cross from 0 to 2V; therefore
a threshold around 1V will allow zero-crossing detection accuracy around 32µs. The
external resistor, say 5MΩ with 110V applied to the pin will limit the current to 38µA,
such limited current is definitely within the safety margin of the PIC chip requirement.
Further more, in order to make sure the chip’s safety, a diode is connected between the
pin and the resistor to clip out negative portion of the sinusoidal AC input, this is
because most of PIC chip pins can only accept input voltage of -0.3V to (VDD + 0.3V)
with respect to VSS.
37
Figure 5-8: Zero-crossing detecting waveform using PIC interface
(a) Input AC signal; (b) Input AC signal across diode; (c) Extract digital square wave input signal with comparator then invert it; (d) Using interrupt to capture the very moment when signal rise.
The above was external installation of the zero-crossing detecting process, the internal
working process of the chip is mainly control using software programmed into it. By
using an existing unique function in PIC16F777 – the comparator; it is a module that
able to perform threshold comparison by either using certain fraction the on-chip
voltage – VDD or supply an external voltage as voltage reference, hence a square wave
output is then generated according to the reference threshold voltage. When a rise signal
38
is detected, the software creates an interrupt and directly store into the RAM for later
phase angle calculation, the capture of interrupt work like a pulse generated at the very
moment when the waveform cross below the threshold voltage. Even though the overall
process will certainly have some delay within the system however it will be small and
would not affect much upon the actual reading. An expecting zero-crossing signal
detecting output is shown in figure 5-8.
5.2.3 ADC and shunt capacitor bank
Conversion of analogue to digital is done within the PIC chip. Such process is done
automatically as PIC chip can only produce digital outputs; the intelligence of the
microchip provides a cinch to PIC programming user, who wants to deliver digital
pulses at output pin. The main task for this section is proper allocation of the output
signal to trigger sufficient shunt capacitors to compensate with leading VAR so that to
improve the connected power system with loads. The overall working principle is
discussed in the flow chart in section 5.3.3
5.3 Design Flow Chart
The designed programs that operate internally in PIC chip are presenting in flow chart
presentation with detail explanations to gain in depth view for this project.
5.3.1 Zero-crossing Detecting Module
As reference in figure 5-8, it was the expecting output pulses of what the following
module should get. Actually the input signal can be rectified into full wave rectified
output using a four diodes bridge circuit but in order to simplify the work for capturing
39
signals between voltage and current since there is possibility that voltage half cycle
might cross zero point before current signal does, it is preferable to block the negative
portion of the sinusoidal signals.
Figure 5-9: Flow chart for zero crossing detector
40
The self-designed zero crossing detector gives priority to detect voltage signal with a
slight delay at beginning so that to ensure the first signal capture would have higher
possibility to detect at crossing zero position instead of somewhere in the middle of
rising edge. With comparator function in the PIC16F777 chip, setting a threshold
voltage of approximate 0.4V using the following equation to extract certain ratio of VDD
as reference voltage as a representation of the threshold voltage.
vefDD CVCVR=×
24
Where, CVR = Comparator reference supply voltage
Cref = Comparator reference voltage (threshold voltage)
Taking CVR = 0010, which equivalent to 2 of decimal as CVR. (2/24) × 5 = 0.41677 V.
Once the threshold voltage is set, the comparator will continuously trace input voltage
and current signals on and on, two trains of pulses with respect to timer are stored into
RAM stacks. Whenever a pulse were created and stored, a flag would trigger so that to
keep track with general clock timer. The voltage flag will continue shooting until the
current flag is detected and stored into RAM as well, then both flags would reset and
begin another round of detection.
41
5.3.2 Phase Angle Computation Module
Figure 5-10: Flow chart for phase angle computation module
After the process of locating the zero crossing positions, determine the phase angle
difference under pure sinusoidal current is now possible. Figure 5-10 is the flow chart
diagram of the phase angle computation.
42
The zero-crossing module sends stored signals into this function module, using general
clock as the main division of two timers. The flags captured in previous mode stored up
records of flag running in term of times. Prior setting of frequency for this system is
8MHz. So the total time interval is
msf
T 125.010811
6 =×
==
Say time difference recorded is 0.025ms, hence the phase angle difference would be
610005.0 ×=−= timevoltagetimecurrentdifferenceTime
02.010125.010005.0
6
6
=××
=elapsedTime
°=°×= 4.1436004.0anglePhase (lagging)
Hence, the power factor, %86.969686.0)1.14cos(cos ==°== θpf
Since most system are lagging in general, thus if current time found to be lower than
voltage, it will reset the system and start all over again.
43
5.3.3 Capacitor bank switching control module
Figure 5-11: Flow chart for Capacitor bank control module
As the power factor has been determine, applied with appropriate mathematic
calculation, the amount of capacitor required to aim for higher power factor output can
44
be found. The mathematic calculating process shall be discussed in the next chapter
with actual reading
The capacitor bank control module is used to decide how many stages of capacitors
should be activated. For a mathematic computed capacitor value, the system will start
comparing that value with the bank stage by stage starting from the lower and smallest
capacitor value. The first detect is if the system is turned on or not, if nothing connected
to the PFC system, this module will order all capacitors to be disconnected and
discharged via the resistors installed in the circuit. Such process done by using the max
capacitor value in the bank deduct the wanted capacitor value, the system will turn all
drivers off if found that the capacitor bank value is the same of the leftover capacitor
value after deduction, then it is confirmed there are no inductive reactance occurs in the
power system or system is remained off.
The way to find out how much capacitor is actually needed for the power system
through the working process of this module, is deduct starting capacitor stages if the
capacitor value is lower than the maximum amount; such process continue until the
required capacitive value of the bank match or close to the wanting value as computed.
An extra feature is to detect how many stage are actually installed into the system, the
remaining available capacitors will continue perform the same process with extra
detection for remaining capacitor in the bank. Note that the minimum installation for
this module is at least three stages.
45
Chapter 6.0: Implementation & Results
6.1 Implementation procedures and target results
The idea is to connect to two types of power system – single-phase and three-phase,
with existence of inductive reactance one at a time in order to test how accurate and
efficient the designed circuit ability to correct the power factor. The level of
improvement and faults would be recorded. For an ideal expectation, the designed
circuit should be able to detect the initial power factor correctly with near zero
uncertainty for each type of assigned power system, which here used a single-phase
power generator with inductor loads and an AC motor. The first testing stage was tested
with fixed inputs.
The next step was to determine the system sensitivity through generate various kind of
inputs. For both single-phase and three-phases power systems, each was tuned up and
down of its input voltage value with reasonable range or varied the loads
simultaneously within a period of time so that to test how sensitive the designed circuit
capable to detect the power factor of the system. With each two major experiment, the
final goal was automatic correcting power factor after extracted power factor and other
necessary parameters information; the improved power factor value would be jobbed
down; since collecting power factor involves capacitor switching and the how much
power factor being improved depends on the amount of capacitor in use hence pre-
calculation is needed for testing purposes.
46
Figure 6-1: Test setting for zero-crossing detector
6.2 Implemented results and discussions
The system design implementation and testing were being divided into three major
parts: Test on zero-crossing detector, test on fixed input system and finally test on a
various inputs system. Since the power factor reading test is different for both single-
phase and three-phase, thus individual testing was carried out in two different sections.
Follow by then is correcting the power factor and this process also distributed in the last
two sub-chapters.
6.2.1 Test on zero-crossing detector module
Figure 6-1 shows the structural configuration to run a test upon the zero-crossing
detector module. Using a model, INSTEK GFG-8020H signal generator to supply a
frequency of 50 Hz and 5V into the PIC microchip at PIN number 2 then set an external
reference voltage using power supply to provides constant DC voltage into PIN number
5, observed the output signal via oscilloscope (model TDS 1012). It should be cautioned
not to over tunning the input voltage more that 5V.
Input voltage signal
Reference voltage
Signal output to oscilloscope
(1) (2) (3)
47
All groundings were connected together with VSS. Meanwhile, the oscilloscope first
channel probe were attached to the input voltage signal port (1) before diode and the
channel two attached to port (1) after diode to find out if the sinusoidal signal were
really clipped the negative portions, then attached to port (3) to monitor the output
waveforms.
Figure 6-2 shows the testing results observed through the oscilloscope. In figure 6-2 (a),
the channel 1 displayed a complete sinusoidal signal while channel 2 was outcome of
input voltage after bypassed the diode before entering into pin port (1), the diode
clipped the negative portion of the sine waveform so that to prevent PIC take in
excessive negative voltage; at the same time, it itself drained some voltage hence
channel 2 waveform was slightly lower. Make sure a shunt resistor of any value must be
connected after the diode and link to ground, this will prevent harmonic appears.
Before obtained the output waveform in figure 6-2 (b), it should be aware that pin 6,
which is RA4 is an open drain output that pull down output signal, thus a pull up
resistor is needed by connecting it to VDD then able come out with desired output. The
DC power supply was connected to port (2) and supplied a reference voltage as
threshold voltage, which is lower than 5V. The reference voltage supplied into port (2)
were 3.74V hence the bandwidth of the square wave rising pulse train was very small.
In order to locate precise zero-crossing point, the threshold voltage were reduced until
reaching approximately 0.524 V before null, the rising edges and falling edges were
almost perfectly drop on every zero points, this are clearly displayed in figure 6-2 (c).
48
Output waveform in figure 6-2 (c) was actually sufficient enough to apply into the
program coding to run the rest of the experiments. However this may not be a satisfied
result compare with the simulated result in figure 5-5, so a slight modification in the
programming code was done using the capture module setting as follow to capture
every finite moment of rising edges and falling edges, a train of perfect zero-crossing
pulses are demonstrated via oscilloscope as shown in figure 6-2 (d).
PIE1 = 0b00000101; // Enable CCP1 & TMR1 overflow interrupt
PIE2 = 0b01000001; // Enable CCP2
CCP1CON = 0b00000101; // Detect every rising edge for voltage
CCP2CON = 0b00000101; // Detect every rising edge for current
Figure 6-3 displays the actual circuit wiring while running the zero-crossing detecting
test after the results demonstrated.
Figure 6-2 (a): Voltage output after diode at the input port.
Output voltage
Input voltage
49
Figure 6.2 (b): Output voltage with VREF = 3.74V
Figure 6.2 (c): Output voltage with VREF = 0.524V
VREF = 3.74V
Output voltage
VREF = 0.524V
Output voltage
50
Figure 6-2 (d): Output voltage after apply capture mode with VREF = 0.5247
Figure 6-3: Actual circuit wiring, the labeling determine the position of results
VREF = 0.524V
Output voltage pulse
(a)
(b) – (d)
51
6.2.2 Test on phase angle detection
This was attempted using an existing induction motor based device – home table fan.
The table fan was connected with an oscilloscope for monitoring the waveforms, a
sensors box (both current transducer and voltage transducer are built inside), and DC
power supply to provide threshold voltage to the PIC. A typical picture is shown in
figure B-6 of appendix B.
The power factor measured for the table fan were quite high, around 0.99234, even
increased its load to the level 3 of its fan rotation. Hence calibration was needed to
obtain a clear view upon the phase changes. During the testing process, the designed
sensor used to test was having a major problem to determine the output. This was
because the converting ratio for the current sensor is 1:1000; while the current exist in
the table were only 0.03A, which after converted would be 30µA. Bypassing with some
resistors and converted into voltage value was not even exceed 0.04 V, such voltage
level would definitely cannot even passed through the diode, which has voltage drop of
0.7V.
The solution was using an operational amplifier - model UA741CP to boost up the input
so that it can be view on screen. A clear picture is shown in figure 6-4 of how the circuit
were connected. The operational amplifier not only serves to amplify the current input
but also can work as a system calibrator. This was a great help for future developing of
the system as the clearly shown the delay occurred in the designed system hence proper
calibration can be done to make the system more perfect.
52
Figure 6-4: Circuit constructed to test phase angle.
The test was simple after solving the problem of low input reading, simply pressed the
button from 0 ~ 3 to observe the changes in phase difference. The LEDs were used to
run a prior test for the next section. The leftmost LED was just used to find out if the
system was running. The red LED was with highest PF – button 1 then follow by button
2 and button 3; the oscilloscope also presented the results as displayed in figure 6-5(a)-
(d). The reason was to run experiment that phase angle can direct affecting the output
without concerning the reactive power. The digital time step differences for PIC to
identify the button were calculated using the following equation:
ns
timeindifferencephasemeasuredsteptime500
= (6 – 1)
Op-Amp
Diode
LEDs correspond to fan buttons
Current input
Voltage input
Voltage (left) and current (right) outputs
53
Figure 6-5 (a): When no button (or button 0) was pressed
Figure 6-5 (b) When button number 1 was pressed
Voltage output
Current output = 0V
Current output
Voltage output
54
Figure 6-5 (c): When button 2 was pressed.
Figure 6-5 (d): When button 3 was pressed.
Current output
Voltage output
Current output
Voltage output
55
Figure 6-4: Block diagram of power factor corretion testing process
6.2.3 Test on fixed input AC power system
6.2.3.1 Single-phase system test procedure
The single-phase fixed input AC power system test is by using an AC voltage regulator
supply unit and applies some loads onto it – resistors and inductor. The frequency of the
supply unit is 50Hz, which directly extracts from normal electrical socket. A typical
testing module was built according to the block diagram as shown in figure 6-4, with
supportive measuring tools to check and to verify the testing outputs with respect to the
PIC chip. The single-phase voltage generator can supply up to 240VAC, but it is a type
that can only be regulated manually by twisting the knob, where percentage values are
labelled on it. The same device will then be used for various inputs test as well.
The first test was supplying a fixed input voltage around 100VAC with different loads.
The main parameters that required determining are: measured phase angles, actual
power factor values, corrected power factor values, number of capacitors triggered.
PIC16F777 phase angle measuring
Single-phase power supply unit
+ Inductive loads
PIC16F777 pf c control process
Capacitor bank
Lab measuring tools
Represents comparison and checking readings
56
Record and tabulate the retrieved parameters into tables and plotting graph to view the
system efficiency.
In this section of testing was with the program to execute power factor correction
process. Unlike the second phase program, the first phase using timer1 as register to
store temporary data. There is a critical situation must a PIC programmer be aware of,
although timer1 is being used as a temporary storage register but it is still a timer that
will continuously running increment until it reaches its limit and overflow, consequently
reset. If programmer ignore this, there are chances that the program being restarted
before finish. Some calculation is needed to avoid the above consequences.
The settling frequency in the PIC oscillator = 8MHz
Only quarter will be used, thus FOSC = 66
1024108
×=× = 2 MHz
For timer1 is a 16-bits register, so 65536216 =
Hence total available time for timer1 to run 1 cycle is
ms768.32sec035768.0102
655366 ==
×
So long the program can accomplish its job that required timer1 before it reset, else the
result retrieved would definitely wrong.
6.2.3.2 Three-phase system test procedure
A three-phase induction motor through an electrical test bed would be a suitable testing
apparatus. It is assumed that unbalance condition is very minute hence the phase angle
differences are technically the same in each line, hence the PFC system would only read
57
a single line current and a line voltage out of the three lines then work out appropriate
calculation to perform suitable power factor correction process. Such assumption were
made because the modules used within microchip, as well as the programmed code
were only capable to take in two inputs for zero-crossing detection and comparison,
hence the parameters to be tested will be the same as single phase, only that the
calculation would be different than the single phase calculation.
6.2.3.3 Overall tested result for fixed input
Although calibration was made during testing with phase angle detection in section
6.2.2 in order to ensure the system run smooth in the rest of testing, however such
attempt still unable to guarantee a nice output; calibration is still needed. Figure B-7 of
appendix B was photo taken for running the test of this section.
Due to insufficient of time proceeding detail testing, the testing stage was done through
observation of LED. The first attempt was supplying 101 VAC to the load of 210 Ω
resistor from the resistive loading bank and 0.67H from the inductive loading bank,
series connection. The calculation below determines the power factor value:
Given HL
RVin
67.0210
0100
=Ω=
°∠=
( )49.210210
67.0502210jj
jXRZ LTotal
+=×××+=
+=π
°−∠=°∠
°∠=
+°∠
== 06.453397.006.4533.297
010049.210210
0101jZ
VIT
%63.707063.006.45cos ===∴PF
58
Supposing the amount of LED lit should be five pieces but the instead it was only three.
Adjustment were made by increasing the threshold of the operational amplifier, also
slight tuning at the PIC threshold voltage. Finally, it was managed to secure up to five
LED but the threshold for operational amplifier seem to be at its limit because if further
increase will lose the signal; hence it was discovered that LED number five kept on
blinking with approximately 4 to 6 seconds each.
A second trial was using two parallel resistors and 4 parallel inductors connected in
series with the source.
%40.89894.0618.26cos
618.268599.06225.52105
1016225.52105
6225.5249.210//49.210//49.210//49.210105210//210
===
−∠=+
==
+=+===
Ω==
PFjZ
VI
jLRZjjjjjL
R
T
T
With calibration done, two LED were lit but the third were slightly blinking as 0.89 PF
is almost 0.90. As a result, the system running considered quite satisfied; it was regret
that unable to construct the capacitor switching. The idea was suppose to drive a
MOSFET directly from the output pins then into the relay to draw connection with the
capacitor banks link with the electric bus.
Since the same application can be assumed applicable in three-phase system wye-
system, hence with the least amount of time in hand, it was suspect it can work quite
well the three-phase system as well.
59
6.2.4 Test on various inputs
This test main concern is the sensitivity of the designed system. The testing process is to
test how fast the system can react when power supply behaves like an emergency power
supply. In other word, the power supply would vary its input in ascending order or
descending order or triggering up and down; certainly this would be done manually.
This part was task for the second phase of the programmed code and testing with the
same appliances used in section 6.2.2.
Unfortunately the desired output cannot be implementing as PIC chip cannot cope with
the changes made. Whenever there were changes made, the power factor reading lost
somewhere, it was suspected that few looping functions within the code were messed
when different voltage inputs supplied. Due to limitation of time, amendment seems
impossible. The second reason, PIC16F777 has no EEPROM to keep history on track;
the timer1 in section 6.2.2 can only perform counting one at a time, if an unpredicted
change appeared just in the middle while detecting phase angle is processing; it will get
a wrong reading or become never ending loop, as a result system completely crashed.
With EEPROM, data storage can perform precise comparison and by averaging the past
results to get power factor to a nearer and reasonable range if system is unstable.
6.3 Review of goals
The tests on fixed voltage input with different loads were considered 60% success
provided the condition that pre-calculation of desired power factor value and supplies
enough shunt capacitors of same value. So far the system only designed of capable to
run switching on maximum 8 stages of capacitors.
60
The various voltage inputs test was not able to accomplish its task however it can be
improved with PIC chip that have EEPROM. If necessary, an external crystal can be
used to rise the clocking frequency thus able to perform a lot of arithmetic calculation,
as well as avoid bus congestion.
61
Chapter 7.0: Future Direction and Conclusion
The testing process did not run test on power converter based systems or synchronous
motor due to required huge amount of expense may need to further enhance the system
to such feature, financial is a critical issue upon further enhancement. Besides, as
discuss in chapter 3 and chapter 4, systems that contain serious harmonic current or ill
non-sinusoidal current would mostly exist in power system with a lot of active
elements.
The final result was not quite the desired output but the idea of making one workable
simple PIC-based power factor correction with the developed system is absolutely
possible.
7.1 Future Direction
In chapter 4 mentioned about power factor correction can be constructed with many and
better approach; as this project did not focus on power system with distorted current or
non-linear waveform system, it is a good idea to further study and getting in depth
knowledge to achieve a better type of power factor corrector using the PIC. The idea of
using converter in for the active power factor circuit was because it can regenerate the
current waveform by amplifier and smoothen it through converter system; such action
with detail understand might can be done with software calibration as well as using PIC
chip to perform suitable control along the circuit. In the present technology, PIC mostly
used as switching control for mainly switched-mode distribution power system,
62
however the increment of green energy had turn the focal point towards renewable
energy and until present era, renewable energy still facing serious problem with poor
power quality, which low power factor is one of the main reasons.
As a result, many firms spent a lot of investment to solve the problem. PIC chip is a
good example of financial solution as one single chip can nearly do everything plus it
only consume very low voltage supply.
63
References
H. Saadat, “Power System Analysis”, Mc Graw Hill, US, 1999. TVPPA group, “Distribution Design Guidelines, Chapter 8 – Capacitors”, pp 256-295,
Booth & Associates Inc., Alexander Publications. ‘FAQ: What is power factor’ 2006. Retrieved 04 July 2006, from
http://www.endpcnoise.com/cgi-bin/e/faqpfc.html
J. M. Bourgeois, ‘Circuit for power factor correction with regards to mains filtering’,
STMicroelectronics, Italy. Retrieved August 23rd, 2006 from http://www.st.com/stonline/products/literature/an/3727.htm
M. Chin 2005, ‘ Power Fundamentals & Recommendations’, pp 5-7, SPCR. Retrieved
September 1st, 2006 from http://www.silentpcreview.com/article28-page5.html ‘K8048 Velleman Board Datasheet’. Retrieved March 10th, 2006, from
http://dev.kewl.org/k8048/k8048/ ‘Power Factor’, LM Photonics Ltd. Retrieved September 8th, 2006 from
http://www.lmphotonics.com/pwrfact.htm ‘Lesson in Electric Circuits – Volume 11, Power Factor ’, Chapter 11. Retrieved May
18th, 2006 from http://www.ibiblio.org/obp/electricCircuits/AC/AC_11.html ‘AN220 – Watt-Hour Meter using PIC16C923 and CS5460’. Retrieved June 5th, 2006
from http://www.microchip.com/stellent/idcplg?IdcService=SS_GET_PAGE&nodeId=1469&filter1=function
‘AN939 – Designing Energy Meter with PIC16F873A’ Retrieved July 25th, 2006 from
http://www.microchip.com/stellent/idcplg?IdcService=SS_GET_PAGE&nodeId=1469&filter1=function
‘AN521 – Interfacing to AC Power lines’. Retrieved August 27th, 2006 from
http://www.microchip.com/stellent/idcplg?IdcService=SS_GET_PAGE&nodeId=1469&filter1=function
64
Appendix A
Program Code
unsigned int Iph;
int ph_diff;
unsigned short x1, x2;
void main ()
OSCCON = 0b01110000; // Use 8MHz
ADCON1 &= 0b11110000; // Clear PCFG0~3 Pins
ADCON1 |= 0b00001011; // RA0-RA3 analogue, RA4-RA7 digitals
T1CON = 0b00000001; // Simply enable TMR1, Prescale 1:1
TRISA = 0b11001111; // set RA4 & RA5 as output, the rest are input
TRISD = 0b00000000; // Set portD as output for ensure chip working
TRISB = 0b00000000; // set portB as output for 2ndary comparator output
// --- zero crossing detector --- //
CMCON = 0b00110101; // select mode 101, invert all input
// --- Power factor computation -- //
65
x1 = 0;
x2 = 0;
if (CMCON.C1OUT == 1 && x1 == 0)
TMR1L = 0; // reset TMR1
TMR1H = 0;
x1 = 1;
x2 = 1;
if (CMCON.C2OUT == 1 && x2 == 1)
Iph = TMR1L;
Iph = TMR1H << 8;
ph_diff = Iph - 0x0000; // compute phase difference
x2 = 0;
if (CMCON.C1OUT == 0 && x2 = 0) //restart all
x1 = 0
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// --- Capacitors Stage Triggering --- //
// phase different calculation with respect to time
// time phase difference = [(angle / 180 deg) / 50 freq ] * 2.0e6
if (ph_diff <= 4043) // pf >= 0.95
PORTB.F1 = 1; // LED RB1 lit to determine no need correction
else if (ph_diff >= 4043 && ph_diff <= 5743) // 0.95 > pf > 0.90
PORTB.F2 = 1; // stage 1 capacitor trigger
else if (ph_diff >= 5743 && ph_diff <= 7064) // 0.90 > pf > 0.85
PORTB.F2 = 1; // stage 1 capacitor trigger
PORTB.F3 = 1; // stage 2 capacitor trigger
else if (ph_diff >= 7064 && ph_diff <= 8193) // 0.85 > pf > 0.80
PORTB.F2 = 1; // stage 1 capacitor trigger
PORTB.F3 = 1; // stage 2 capacitor trigger
PORTB.F4 = 1; // stage 3 capacitor trigger
else if (ph_diff >= 8193 && ph_diff <= 9202) // 0.80 > pf > 0.75
PORTB.F2 = 1; // stage 1 capacitor trigger
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PORTB.F3 = 1; // stage 2 capacitor trigger
PORTB.F4 = 1; // stage 3 capacitor trigger
PORTB.F5 = 1; // stage 4 capacitor trigger
else if (ph_diff >= 9202 && ph_diff <= 11806) // 0.75 > pf > 0.60
PORTB.F2 = 1; // stage 1 capacitor trigger
PORTB.F3 = 1; // stage 2 capacitor trigger
PORTB.F4 = 1; // stage 3 capacitor trigger
PORTB.F5 = 1; // stage 4 capacitor trigger
PORTB.F6 = 1; // stage 5 capacitor trigger
else if (ph_diff >= 11806) // pf < 0.6
PORTB.F2 = 1; // stage 1 capacitor trigger
PORTB.F3 = 1; // stage 2 capacitor trigger
PORTB.F4 = 1; // stage 3 capacitor trigger
PORTB.F5 = 1; // stage 4 capacitor trigger
PORTB.F6 = 1; // stage 5 capacitor trigger
PORTB.F7 = 1; // stage 6 capacitor trigger
else PORTD.F1 = 1; // indicate pf exceed below 0.6
while (1)
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PORTD.F0 = ~PORTD.F0; // Ensure MCU working
delay_ms(1000); */
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Appendix B
PIC16F777 microchip
Figure B-1: PIC16F777 Microcontroller chip
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MikroC version 6.0 program overview
Figure B-2: MikroC microchip programming software
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WinPIC software (DL4YHF's PIC Programmer for Windows)
Figure B-3: Win PIC programmer microchip interface software
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Test on Zero-crossing Circuit (Built circuit and result)
Figure B-4: Zero-crossing circuit hardware structure
Figure B-5: Output waveforms of above circuit
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Environment of phase angle testing progress
Figure B-6: Picture taken when testing phase angle using induction motor (table fan)
Environment of single phase power factor testing progress
Figure B-7: Testing for single phase variable loads
Single-phase voltage regulator
PIC circuit
Sensors
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Appendix C
Sample of actual PFC 3-phase connection diagram
Figure C-1: 3-Phase system cable connection (TCS Perunding Ltd. Co.)