resonant & multimode sc...
TRANSCRIPT
Jason T. Stauth, Assistant Professor([email protected])
IEEE PowerSOC, October 5, 2016
Resonant & Multimode SC Converters:Power Management in the mm3 Regime
Outline
• High-density DC-DC conversion• Hybrid/Resonant Topology Overview• Generalized output impedance modelling for N:1
resonant topologies• Multimode operation• SC/ReSC power loss minimization & comparison• Example: 12V 3.7V Quasiresonant Series-
Parallel Converter• Conclusion
2
outsw
ppppout
sw
inpp
Cfi
v
LfVi
∆∝∆
∝∆
,
High Density DC-DC Converter:
3
Strategy 1: Increase frequency Smaller inductor, capacitor Increase in frequency dependent
losses (winding, core, gate drive etc.)
Strategy 2: Change Architecture Reduce inductor ΔV Multi-level or multi-stage converter Possible double efficiency penalty
Do Both?
−
→
−
→
FsA
HsV
IOUT
L Vout
iLS2
S1
Vin C IOUTC
L Vout
iLS2
S1
Vin
N:1
Key → Reduce passive component volume
Switched Capacitor Perspective
Only switches and capacitors Simple full integration in standard
CMOS
Capacitors have much higher energy density than inductors Stacked devices enable high
voltage with low voltage process Achieve higher device utilization
FOM1
Inherent charge sharing loss Difficult Regulation
Reconfigurable Architectures Lossy linear regulation
4
Spec
ific
Volu
me
(mm
3 / µJ
)
Specific Cost ($/ µJ)
Inductor
Capacitor
Accessing this energy density costs power
1[Seeman & Sanders, TPEL 2008]
+V1
-
+V2
-2
21 VCEloss ∆=
[Cooley & Leeb, APEC 2011]
Hybrid/Resonant SC Converters
5
CL
IL
VOUTSC Stage
e.g. FCML [1, 3], Series Parallel [2], Fibonacci, Dickson [3]
Leverage high active device utilization (same as SC) Soft charging or resonant energy
transfer (reduce charge sharing loss) Potential for higher utilization of
capacitor energy density (larger voltage swing allowed) SC front end lower V-s product shrink inductor dramatically Capability for Variable Regulation Multi-mode operation: high
efficiency across load range[1] Meynard PESC ‘92[2] Schaef APEC ‘17[3] Lei et al & PilawaAPEC ’16 & TPEL ‘15
(Concept can be generalized to many topologies)
[Kesarwani Compel ’15][Rentmeister ECCE ‘16]
Dickson ReSCSeries-Parallel ReSC
Examples
[Lei et al, COMPEL 2013]
COUT
VOUT
IDC
LX
SP
SP
SP
SP
SN
SN
SN
SN
Cx1CX2
VDD
CX3
i x
FCML/Meynard
CX1ix
SWCX2CX3
VDD
COUT
VOUTLX
IDC
S1
S2
S3
S4
S5
S6
S7
S8
Considerations: • Internal Charge Sharing• Voltage Balance on Capacitors = universal challenge• Startup, gate driving• Variable control & timing• Parasitics, ringing, etc.
[Kesarwani, COMPEL ‘15]Implementation is challenging, but performance is compelling
CX
1
S
P
S
COUT
VOUT
LX
CX
2C
X3
PP
S
S
PP
P
IDC
ix
VDD
VSW
VOUTix
CX1 CX2 CX3
State 1
VSW
VOUTVDD
VOUTix
CX1 CX2 CX3
State 2
VSW
6
Pilawa, Perreault (JSSC 2012)
Kim, Brooks, Wei(JSSC 2012)
FCML: Meynard ’92
Schaef, Stauth,(ISSCC 2015)
Lei, May, Pilawa(TPEL 2016)Pique, Alarcon
(PESC 2008)
Yousefzadeh, Alarcon, Maksimovic (TPEL 2006)
Examples: Past Work
7
(& others, e.g. Pilawa Little BoxAPEC ‘16)
Lx
iLx
C1C2CN-2S1
S1*
S2
S2*
SN-2
SN-2*
SN-1
SN-1*
Vout
Many other examples, esp FCML, 3-level:Reusch & Lee; Salem & Mercier; Shenoy et al;
General formulation: Step-Down Topologies SC = unregulated, arbitrary N:1 step down stage Inductive impedance shapes the current waveform Reff model: captures conduction loss & loadline
Generalized Output Impedance Modelling
8
Focus: Hybrid SC topologies that can be resonated with a single inductor (FCML, Series Parallel, Fibonacci)
+Vin-
+Vout
-
Reff
Iout
N:1
In Any Given Phase…
9
Vi VoutIi
RiCi
Vi VoutIi
RiCi L
𝐼𝐼𝑖𝑖 𝑡𝑡 = 𝑘𝑘𝑖𝑖𝑒𝑒−𝑡𝑡𝑅𝑅𝑖𝑖𝐶𝐶𝑖𝑖 𝐼𝐼𝑖𝑖 𝑡𝑡 = 𝑘𝑘𝑖𝑖𝑒𝑒
−𝑡𝑡𝑅𝑅𝑖𝑖2𝐿𝐿 sin 𝜔𝜔0𝑖𝑖𝑡𝑡
Key: 𝑞𝑞𝑖𝑖 = �0
𝑡𝑡𝑖𝑖𝐼𝐼𝑖𝑖 𝑑𝑑𝑡𝑡 𝐸𝐸𝑖𝑖 = �
0
𝑡𝑡𝑖𝑖𝑅𝑅𝑖𝑖𝐼𝐼𝑖𝑖2 𝑑𝑑𝑡𝑡
Charge Transferred: Energy Dissipated:
𝑡𝑡𝑖𝑖 =𝑇𝑇𝑠𝑠𝑠𝑠
2 =1
2𝑓𝑓𝑠𝑠𝑠𝑠
e.g. 2:1
)conditions initial(Fki =
Reff Model
10
𝑅𝑅𝑒𝑒𝑒𝑒𝑒𝑒 =𝑓𝑓𝑠𝑠𝑠𝑠 ∑𝐸𝐸𝑖𝑖𝑓𝑓𝑠𝑠𝑠𝑠 ∑𝑞𝑞𝑖𝑖 2
𝑃𝑃𝑙𝑙𝑙𝑙𝑠𝑠𝑠𝑠 = 𝑓𝑓𝑠𝑠𝑠𝑠�𝐸𝐸𝑖𝑖
𝑞𝑞𝑖𝑖 = 𝑎𝑎𝑖𝑖 𝑞𝑞𝑟𝑟𝑒𝑒𝑒𝑒Know proportionally how much charge flows out in each phase from topology
Same as aout element in:[Seeman & Sanders, TPEL ’08]
Cancels out in final calculation, sort of arbitrary
+Vin-
+Vout
-
Reff
Iout
𝑒𝑒.𝑔𝑔. : 𝑞𝑞𝑟𝑟𝑒𝑒𝑒𝑒= �𝑞𝑞𝑖𝑖
= 𝐼𝐼𝐷𝐷𝐶𝐶2 𝑅𝑅𝑒𝑒𝑒𝑒𝑒𝑒 = 𝑓𝑓𝑠𝑠𝑠𝑠�𝑞𝑞𝑖𝑖
2
𝑅𝑅𝑒𝑒𝑒𝑒𝑒𝑒
*optimized/normalized cap sizing/utilization*normalized Tsw/τ per phase
Results
11
Arbitrary SC Circuit
𝑅𝑅𝑒𝑒𝑒𝑒𝑒𝑒 =∑𝑎𝑎𝑖𝑖
2
𝐶𝐶𝑖𝑖coth 𝑡𝑡𝑖𝑖
2𝑅𝑅𝑖𝑖𝐶𝐶𝑖𝑖2𝑓𝑓𝑠𝑠𝑠𝑠 ∑𝑎𝑎𝑖𝑖 2
𝑅𝑅𝑆𝑆𝑆𝑆𝐿𝐿 =∑𝑎𝑎𝑖𝑖
2
𝐶𝐶𝑖𝑖2𝑓𝑓𝑠𝑠𝑠𝑠 ∑𝑎𝑎𝑖𝑖 2 𝑅𝑅𝐹𝐹𝑆𝑆𝐿𝐿 =
∑𝑎𝑎𝑖𝑖2𝑅𝑅𝑖𝑖𝑡𝑡𝑖𝑖
𝑓𝑓𝑠𝑠𝑠𝑠 ∑𝑎𝑎𝑖𝑖 2
𝑡𝑡𝑖𝑖 ≫ 2𝑅𝑅𝑖𝑖𝐶𝐶𝑖𝑖 𝑡𝑡𝑖𝑖 ≪ 2𝑅𝑅𝑖𝑖𝐶𝐶𝑖𝑖
𝑅𝑅𝑒𝑒𝑒𝑒𝑒𝑒,𝑅𝑅𝑒𝑒𝑆𝑆𝐶𝐶 =∑𝑎𝑎𝑖𝑖
2
𝐶𝐶𝑖𝑖tanh 𝑅𝑅𝑖𝑖
8𝐿𝐿𝑓𝑓0𝑖𝑖2𝑓𝑓𝑠𝑠𝑠𝑠 ∑𝑎𝑎𝑖𝑖 2
𝑅𝑅𝑒𝑒𝑒𝑒𝑒𝑒,𝑅𝑅𝑒𝑒𝑆𝑆𝐶𝐶 ≈∑ 𝜋𝜋𝑎𝑎𝑖𝑖24𝐶𝐶𝑖𝑖𝑄𝑄𝑖𝑖
2𝑓𝑓𝑠𝑠𝑠𝑠 ∑𝑎𝑎𝑖𝑖 2
Arbitrary ReSC Circuit
@ high Q
e.g. 2:1 ai = 1, Ci = C, Ri = R
𝑅𝑅𝑆𝑆𝑆𝑆𝐿𝐿 =1
4𝑓𝑓𝑠𝑠𝑠𝑠𝐶𝐶𝑅𝑅𝐹𝐹𝑆𝑆𝐿𝐿 = 𝑅𝑅
e.g. 2:1 ai = 1, Ci = C, Ri = R, Qi= (ωoRC)-1
𝑅𝑅𝑒𝑒𝑒𝑒𝑒𝑒,𝑅𝑅𝑒𝑒𝑆𝑆𝐶𝐶 ≈𝜋𝜋2
8𝑅𝑅
Note: Result is general • Works for arbitrary N-level SC/ReSC topologies where charge flow links the
output: SP, FCML, Fibonacci• Specific cases (Series parallel, FCML) worked out in: [Pasternak, Compel ‘16]
𝑅𝑅𝑅𝑅𝑒𝑒𝑆𝑆𝐶𝐶 =∑ 𝜋𝜋𝑎𝑎𝑖𝑖24𝐶𝐶𝑖𝑖𝑄𝑄𝑖𝑖
2𝑓𝑓𝑠𝑠𝑠𝑠 ∑𝑎𝑎𝑖𝑖 2𝑅𝑅𝑆𝑆𝑆𝑆𝐿𝐿 =∑𝑎𝑎𝑖𝑖
2
𝐶𝐶𝑖𝑖2𝑓𝑓𝑠𝑠𝑠𝑠 ∑𝑎𝑎𝑖𝑖 2
In SSL @ same frequency, Reff of resonant case is improved by a factor of ~ 𝝅𝝅𝟒𝟒𝑸𝑸𝒊𝒊
SC FSL/SSL boundary at 𝑡𝑡𝑖𝑖 = 2𝑅𝑅𝑖𝑖𝐶𝐶𝑖𝑖 For ReSC 𝑡𝑡𝑖𝑖 ≈ 𝜋𝜋 𝐿𝐿𝐶𝐶𝑖𝑖
@ inflection, resonant period is increased (frequency is reduced) by ~ 𝝅𝝅𝟐𝟐𝑸𝑸𝒊𝒊
Comparison(any arbitrary converter or phase)
• Fundamental resonant operation = primary case treated thus far
• @ high frequency CCM
• @ low frequency off-time modulation (DCM)
• Behavioral model can be used tocapture entire frequency range:
• α=9.2 (least squares analysis)
• Less than 2% error over entire range
ESRSW
EFF RffR α
απ
+≈ 0
2
81
DCM
Resonant
CCM
𝑅𝑅𝑒𝑒𝑒𝑒𝑒𝑒 =1
4𝐶𝐶𝑓𝑓𝑠𝑠𝑠𝑠
sinh 𝑅𝑅4𝐿𝐿𝑓𝑓𝑠𝑠𝑠𝑠
+ 𝑅𝑅4𝜋𝜋𝐿𝐿𝑓𝑓0
sin 𝜋𝜋𝑓𝑓0𝑓𝑓𝑠𝑠𝑠𝑠
cosh 𝑅𝑅4𝐿𝐿𝑓𝑓𝑠𝑠𝑠𝑠
− cos 𝜋𝜋𝑓𝑓0𝑓𝑓𝑠𝑠𝑠𝑠
Reff vs Frequency: Any Arbitrary Phase
13
Exact Expression –> 2:1 Converter:
~Q
~Q
Resonant operation indexes performance across all modes!
[Kesarwani, ISSCC ‘14]
[Pasternak, Compel ‘16]
Extended Multimode Operation
14
N:1SC
+
Vin
-
+Vsw-
+Vout
-
iL
Iout
L
Co
Variable regulation• Interpolate between levels:
• Depending on volt-seconds applied(frequency and Vsw-Vout)Inductor current waveform will appear:
111
−<<
−−
Nk
VV
Nk
in
outThis is a conceptual drawing, not schematically accurate
11 −<< Nkfor:
Nice way to accomplish multi-mode operation: Current Mode Control
N:1SC
+Vin-
iL
L
Co
Av
Ac
Gv
Gc
Syncronization, level shift, gate
drive
Vout
Iload
Cur
rent
Time
Ipeak
Ivalley
High-ish Load: CCM
Light-ish Load: DCM
Cur
rent
Time
Ipeak
Nice bonus: This scheme can ‘automatically’ balance flying capacitor voltages!
[Rentmeister ECCE ‘16]
SC Optimization
IDCV1
REFF2:1
PSW SWCONDLOSS PPP += SWGGEFFDC fERI += 2
Related to Rswitch, ↓ with ↑ size
Related to Cswitch, ↑ with ↑ size
16
=
RCfCfR
SWSWEFF 4
1coth4
1swspGGGG WEE ,4=
𝑅𝑅 =2𝑅𝑅𝑙𝑙𝑜𝑜,𝑠𝑠𝑠𝑠
𝑊𝑊𝑠𝑠𝑠𝑠
+= −
SPONXSWSPGGDC
DCSWSPONXopt
RCfEIIfRCW
,23
,2
1,
128tanh8
⇓
=∂∂ 0
sw
LOSS
WP
[Kesarwani, TPEL ’14]
This is true regardless of static loss, fixed resistance, bottom plate capacitance
C1
C2
M1
M2
M3
M4
VG
VG
VG’
VG’
RESR
CXIDC
Vout ix
VDD
SC Optimization
IDCV1
REFF2:1
PSW SWCONDLOSS PPP += SWGGEFFDC fERI += 2
17
)( swopt fFW =
0=∂∂
sw
LOSS
fP
3
,,2
2
, 128 SPONSPGGX
DCOPTSW REC
kIf = 𝑘𝑘 = 0.577
=+ −
kkk 1sinh
21 1
equation? ntal trancende⇒
3
,,2
2
, 1652.0SPONSPGGX
DCOPTSW REC
If = 3
,
22
4386.1SPGG
onspDCXopt E
RICW ⋅=
3,,3/4850966.2
X
SPONSPGGDCLOSS C
REIP ⋅⋅=
Device FOM
[Pasternak, Compel ’16]
Note: does not include bottom plate loss… lets discuss later!
ReSC Optimization
IDCV1
REFF2:1
PSW SWCONDLOSS PPP += SWGGEFFDC fERI += 2
18
sw
sponEFF W
RR ,
2 28π
=swspGGGG WEE ,4=
⇒=∂∂ 0
sw
LOSS
WP
spGG
spon
SWDCopt E
Rf
IW,
,14π
=
spGGsponSWDCMIN ERfIP ,,2π=
, =optSWf 0?
RESR
CX
IDC
Vout
ix
VDD
LX
CBP
CBP
VSW
M1
M2
M3
M4
S1*
S1
S2
S2*
• Says that ReSC (and other hybrids) get better with arbitrarily low frequency, independent of other factors…
• What is happening solution is choosing arbitrarily large, lossless inductor!
Device FOM
Btw: similar optimizations for N:1 topologies in Pasternak ‘16
Realistic Inductor Model
actAC
DCDC
fkR
RR
LL
0*
0*0
0,*0,
0*0
=
=
=
=
εε
ε
000
000,
00,
00
V,f @ Q base
V,f @ R base
Vfreq, low @ R base
V @ L base
=
=
=
=
Q
R
RL
AC
DC
000
000,
2 fkQ
LfRAC ==π
Neglects RDC other models possible
Dimensional Scaling:
x ε
x ε
x ε
Same turns ratio
ερ 1
∝Al
ε2NL ∝
Invariant RAC (const f0), larger L
Constant Volume Scaling of Inductance
00,
2
00,
2
2
LLRNR
LLRNR
NL
actACAC
actDCDC
=∝
=∝
∝
[Perreault et al and Sullivan APEC ‘09] 19
SC and ReSC Optimization
IDCV1
REFF2:1
PSW SWCONDLOSS PPP +=
Total Power Loss
ReSC is practical with mm-scale air-core inductors!Must achieve sufficient ‘Q’ to have an advantage
[Largely unpublished]
Pow
er L
oss (
norm
aliz
ed)
fsw/fFSL
Larger Smaller
Ideal inductor model
Real inductor models
Here:• Every point is optimal @ fsw• Fixed capacitance• Includes bottom plate loss
20
spGGsponSWMIN ERfP ,,∝
x ε
x ε
x ε
[Scaling Laws: Perreault et al and Sullivan, APEC ‘09]
Example: 12V 3.7V (LiIon) Quasiresonant Series Parallel
21
M1,2
M3
M4M5
M6M7
M8
Cin
startup control,pulse gen.
gate drivers
Details
22
• Regulation: 1-bit voltage-mode integral control with nested zero current detection
• Inductor = 33 nH (0402)• Flying Cap = 2 x 330 nF (0402)• Bypass Cap = (0201) input, (0402) output• Peak efficiency = 87% @ 4.6 W• Power density = 0.3 W/mm3 ≈ 5.0 kW/in3
(bounding box)
Current (A)
Conclusion
• Hybrid/Resonant SC topologies = great candidate high-density dc-dc converter
• Arbitrary N:1 converter output impedance a useful tool for analysis and comparison
• Quality Factor indexes performance in all modes, (without Q, you have nothing!)
• Multimode operation: great option for high efficiency across load range
• Any reasonable comparison must factor in the inductor: larger is better, but Q is the key driver
23
Thanks
24
This work was supported in part by NSF grants:ECCS 1309905, ECCS-1407725, ECCS 1554265 (CAREER)