rf system design and simulation using gan 12 & 13 march...
TRANSCRIPT
Presented by
Bhupinder Singh
RF system design and simulation using GaN12 & 13 March 2015
Finetuning Academy (www.finetuningrf.com)
Learning Objectives RF System design – Basics, Simulation using ADS – Advanced Techniques
Using Non-Linear Models to design the PA Circuit
Design Constraints for different Modulation Schemes like QPSK, QAM, OFDM
Design of RF Power Amplifier using GaN HEMT in Pulsed / CW mode
Design of RF Power Amplifier using GaN HEMT in Doherty configuration
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Course Description
This 2-Day workshop addresses the following key areas: Overview of RF System design, RF system simulation using ADS, GaN HEMT based PA simulation using non-linear models in ADS, PA circuit design in CW / Pulse mode, Doherty PA Configuration using GaN devices
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• Schedule
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Topics, Mar-12, Thursday Time
Power Amplifier - Efficiency and Linearity enhancement
Techniques900-1030
Tea Break 1030-1045
Power Amplifier - Efficiency and Linearity enhancement
Techniques1045-1115
GaN Power amplifier design with Simulation examples (CW
Mode, Broadband)1115-1300
Lunch Break 1300-1345
GaN Power amplifier design with Simulation examples (Doherty
Configuration)1345-1500
Tea Break 1500-1515
GaN based PA design, Die version, in Ku-band 1515-1630
Interactive Session 1630-1700
Topics, Mar-13, Friday Time
RF System design - Introduction 900-1030
Tea Break 1030-1045
RF System design and Simulations using ADS 1045-1300
Lunch Break 1300-1345
RF System design and Simulations using ADS 1345-1500
Tea Break 1500-1515
RF System design and Simulations using ADS 1515-1630
Interactive Session 1630-1700
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• Bhupinder Singh received his Master’s Degree in Microwave System Design from IIT Kanpur, Kanpur India. He has 23 years of RF system / subsystem design, development and testing for Govt, Military, and Cellular and VSAT industry. He is currently Director-Technical at RF Specialities. He was a scientist at Aeronautical Development Establishment from 1991-2001. Previously he was RF Design Lead at HFCL, DMC-STRATEX, Blackbay, Technical Head-Telecom R&D at Astra MWP, Eminent Systems. He is an advanced user of Simulation tools like ADS, MWO, ALTIUM and ACAD. He is skilled at using Spectrum Analyzer, NW Analyzer, Vector Signal Analyzers, signal generators. RF Specialities (RFS) is one of the leading companies in the development, design, servicing and maintenance of RF Equipment in India. Boasting of a state-of-the-art RF laboratory and backed with experienced & well-trained manpower, it provides unique and cost-effective solutions in the shortest turn-around time for the satellite, broadcasting, telecom and military industry.
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Speaker
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• Module-1: RF Power Amplifier▫ PA Fundamentals
▫ GaN Technology – Properties
▫ PA Design Steps, Device Selection and Model
▫ Simulated Load Pull
▫ PA Measurement
▫ One Tone and Two Tone IMD
▫ ACPR WCDMA (PAR 6dB)
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• Module-2: RF Power Amplifier Efficiency Enhancement Techniques▫ Doherty PA – Conventional and Modified
▫ Envelope Elimination and Restoration
▫ BIAS Adaption
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• Module-3: RF Power Amplifier Linearization Techniques▫ PA Characterization
▫ Digital Communication System
▫ Feedforward Linearizer
▫ Digital Pre-distortion
▫ Adaptive Digital Pre-distortion
▫ Adaptive Digital Pre-distortion at IF
▫ Adaptive Digital Pre-distortion at Baseband
7
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• Topic 4: RF System Design▫ Analog Transceiver Parameters
▫ Noise Figure
▫ Noise Figure of Cascade
▫ Equivalent Noise Temperature
▫ 1-db Compression
▫ Dynamic Range
▫ IMD
▫ Digital Modulated System
▫ BER
▫ QAM System – Primary Noise and Distortion Elements
▫ Effect of Source Phase Noise
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• Q and A Session
• Quiz to assess how much information participants learned
• Survey participants to see if they found the training beneficial
Assessment and Evaluation
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Presented by
Bhupinder Singh
MODIFIED DPA USING GaN TRANSISTOR
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INTRODUCTION
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• Power Amplifiers for Efficiency and Power Output
• BJTs, GaAsFETs, VDMOS, LDMOS, GaN
• Controlled source and switched mode PA
• Modes of Operation for controlled source PAs : A, B, AB, C
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PA FUNDAMENTALS
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ASSUMPTIONS • Load is purely resistive • All harmonics shorted • Constant trans
conductance (𝒈𝒎 ) • Knee voltage is small
compared with drain voltage
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PA FUNDAMENTALS
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Class-A
𝐼𝐷𝐶= 𝐼𝐷𝑄 =𝑣𝑑𝑠,𝑚𝑎𝑥
𝑅=
𝑉𝐷𝐷
𝑅
𝑃𝑑𝑐 = 𝑉𝐷𝐷𝐼𝐷𝐶 = 𝑉𝐷𝐷2
𝑅
𝑃𝑜,𝑚𝑎𝑥= 𝑣𝑑𝑠,𝑚𝑎𝑥2
2𝑅 =
𝑉𝐷𝐷2
2𝑅
η = 𝑃𝑜,𝑚𝑎𝑥
𝑃𝑑𝑐 =
1
2 = 50%
𝑉𝑑𝑠,𝑚𝑎𝑥= 2𝑉𝐷𝐷
𝐼𝑑𝑠,𝑚𝑎𝑥= 2𝐼𝐷𝑄 = 2𝑉𝐷𝐷
𝑅
𝑃𝑚𝑎𝑥= 𝑃𝑜,𝑚𝑎𝑥
𝑉𝑑𝑠,𝑚𝑎𝑥𝐼𝑑𝑠,𝑚𝑎𝑥= 1
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Class-B
𝐼𝐷𝐶= 𝐼𝑑𝑠,𝑚𝑎𝑥
π ; 𝐼1=
𝐼𝑑𝑠,𝑚𝑎𝑥
2
𝑃𝑑𝑐 = 𝑉𝐷𝐷𝐼𝐷𝐶 = 𝑉𝐷𝐷𝐼𝑑𝑠,𝑚𝑎𝑥
π
𝑃𝑜 = 𝑉𝐷𝐷
2𝐼1 =
𝑉𝐷𝐷
2 𝐼𝑑𝑠,𝑚𝑎𝑥
2
η = 𝑃𝑜,𝑚𝑎𝑥
𝑃𝑑𝑐 =
𝜋
4 = 78.5%
𝑃𝑚𝑎𝑥= 𝑃𝑜,𝑚𝑎𝑥
𝑉𝑑𝑠,𝑚𝑎𝑥𝐼𝑑𝑠,𝑚𝑎𝑥= 1
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PA FUNDAMENTALS
5
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PA FUNDAMENTALS
6
Class C
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PA FUNDAMENTALS
7
𝛟 is the current conduction angle (CCA)
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PA FUNDAMENTALS
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PA FUNDAMENTALS
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Optimum load at fundamental frequency is given by
opt
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SEMICONDUCTOR PROPERTIES
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SEMICONDUCTOR PROPERTIES
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Design steps for PA realization
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PA DEVICE SELECTION
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PA DEVICE SELECTION
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PA MODEL
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SIMULATED LOAD PULL
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SIMULATED LOAD PULL
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SIMULATED LOAD PULL
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PA MEASUREMENT
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• One tone measurement : AM-AM and AM-PM distortion
• Two tone measurement : IMD (typically 30dbc for constant envelope modulation)
• ACPR, EVM, CCDF are metrics for Digitally modulated signal
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Two Tone IMD Measurement
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One Tone Measurement
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ACPR WCDMA (PAR 6db)
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Presented by
Bhupinder Singh
PA EFFICIENCY ENHANCEMENT TECHNIQUES
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• Modern Communication systems demand high PAR
• High Efficiency
• Multiband –Multi standard operation
• Better linearity
• DOHERTY POWER AMPLIFIER
• ENVELOPE ELIMINATION AND RESTORTION
• BIAS ADAPTION
Introduction
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DOHERTY PA
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ENVELOPE ELIMINATION AND RESTORTION
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BIAS ADAPTION
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• Ideal efficiency value 78.5% at maximum power output
• Efficiency decreases as the input drive level is reduced
• η= Pi/4*p ; p is the reduction in input voltage drive
• Increase the load resistance by same factor p its possible to return to ideal efficiency value of 78.5%
Ideal Class B Amplifier
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• Active load pull concept, dynamically alters the load resistance for maximum efficiency
• Extends high efficiency operation to lower power levels
• 𝑍1=𝑅𝐿*(1 +𝐼2
𝐼1 )
Conventional Doherty PA
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• Three distinct operating regions are defined for DPA
• Low Drive region: Carrier amp conducting Peaking amp OFF
• Load Modulation Region: Carrier saturated Peaking turning ON
• Peak Power Region: Carrier and Peaking amplifiers saturated
Conventional Doherty PA
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Conventional Doherty PA
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Theory of operation
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𝐈′𝐋
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Theory of operation
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• 𝐼3 = 𝐼1𝑅1
𝑅3 ----(1)
• 𝐼3 = 𝑅2
𝑅2+𝑅3𝐼′𝐿 ; 𝐼2 =
𝑅3
𝑅2+𝑅3𝐼′𝐿
• 𝐼′𝐿 = 𝐼2 + 𝐼3 = 𝐼3(𝐼2
𝐼3+1) =
𝐼3
𝛽 ; where β is the current division ratio
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Theory of operation
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impedance seen at the output of the Carrier amplifier is
• 𝑅3 = 𝐼3+𝐼2
𝐼3
𝑍12
𝑅𝐿 =
𝑍12
𝛽𝑅𝐿 (2)
And the impedance seen at the output of the Peaking amplifier is
• 𝑅2 = 𝐼3+𝐼2
𝐼2
𝑍12
𝑅𝐿 =
𝑍12
(1−𝛽)𝑅𝐿 (3)
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Theory of operation
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• Case-1 (Symmetric Doherty)
current and power division ratios of α=β=0.5
𝑅1= 𝑅2=𝑅3=𝑍2=2𝑍1
2
𝑅𝐿 in Peak Power Region
• for 𝑍1=35 𝛀 and 𝑅𝐿=50 𝛀
• 𝑅1= 𝑅2=𝑅3=𝑍2 = 50 𝛀
• In low power region
𝑅1=𝑍22
𝑍12 𝑅𝐿=100 𝛀 (6db back-off)
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Theory of operation
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• Case-2 (Asymmetric Doherty)
current and power division ratios of α=β=0.25
𝑅1= 𝑍2=𝑅3=3𝑅2; in Peak Power Region
for 𝑍1=15 𝛀 and 𝑅𝐿=50 𝛀
• 𝑅1=𝑍2=18 𝛀; 𝑅2=𝑅3/3=6 𝛀
• In low power region
𝑅1=𝑍22
𝛃𝑅3=72𝛀 (12db back-off)
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Limitations of Conventional DPA
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• In the low power region, the assumption of Peaking Amplifier being open is difficult to achieve
• The power splitter and combiner at the input and output of the DPA are inherently narrowband due to the presence of lambda by four transformers
• The Peaking and Carrier amplifiers are to be designed using wideband matching techniques
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Modified DPA
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• Simple modifications to improve operating BW of Conventional DPA
• 30% operating BW centered around 1450MHz till 6db back-off
• Cree CGH40045 GaN transistor for Carrier (Class AB) and Peaking Amplifier (Class C)
• Symmetric DPA structure
• Better than 30% efficiency over full BW and 6-db Back-off range
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Modified DPA
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• The Carrier and Peaking amplifier were designed over a broad range of frequencies 1.2GHz-1.8GHz. ADS simulations were carried out to check and optimize the performance of Carrier and Peaking amplifier over this frequency range
• Replacing the 50 ohms impedance inverter at the output of Carrier amplifier by a 70 Ohms impedance inverter, inserting another 70 ohms impedance inverter at the Peaking amplifier output and removing the 35 ohms Impedance transformer at the load. The load is now directly connected at the junction of two 70 Ohms impedance inverters.
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Modified DPA
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Modified DPA
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• The relatively smaller impedance step (from 50 ohms to 100 ohms) at the output of Carrier amplifier improves the BW by a factor of 1.73.
• The power splitter at the input is a modification of Branch line hybrid where additional lambda by four sections are included to make it operate over octave band (1G-2G) without changing its size appreciably
• Offset delay lines were included at the output of the Carrier and the Peaking amplifier
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Modified DPA
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Modified DPA
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Modified DPA
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DISCUSSION OF SIMULATION RESULTS
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• Modified DPA delivers good efficiency over a broad BW
• Demonstrates Linearity improvement over Class AB amplifier
• Suffers from BW limitation of output combiner
• Further improvement possible by designing a wideband output combiner to covet the entire 0.8G to 2.7G cellular band
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Result Discussion
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Result Discussion
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Result Discussion
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Result Discussion
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ACPR RESPONSE OF MODIFIED DPA
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Result Discussion
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ACPR RESPONSE OF CLASS AB PA
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POWER AMPLIFIER LINEARIZATION TECHNIQUES
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PA CHARCTERIZATION
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• PAs differ in values of coefficients 𝑎3 and 𝑎5 resulting in different looking AM-PM curves
• Coefficients 𝑎3 and 𝑎5 are higher for amplifier with higher AM-PM distortion
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PA CHARACTERIZATION
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• Asymmetry in IMD • Due to time lag or phase shift as
measured in the envelope time domain, between the AM-AM and AM-PM response
• Phase change is mainly caused by C-V characteristics of gate source junction
• Reducing gate source capacitance will reduce AM-PM and hence IMD asymmetry
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PA CHARACTERIZATION
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• AM-PM is significantly more in devices operating in Class AB mode where quiescent point is closer to region of maximum phase variation
• AM-PM is greatly reduced in GaN devices because of higher power density and smaller gate periphery
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DIGITAL COMMUNICATION SYSTEM
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• Peak power substantially higher than Average power
• Peaks are very infrequent • Time trajectory driven by distinct
“beat” or symbol clock • Two time domains: first shows
individual RF carrier variations and the second shows carrier modulation(Envelope Domain)
• Amplitude or Phase Distortion results in spectral spreading of signal
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DIGITAL COMMUNICATION SYSTEM
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• As the PA distorts, alleviates distortion by driving PA harder
• No more headroom for improvement near saturation
• Signal emerging from pre-distorter will be highly distorted like uncompensated PA necessitating the use of high speed digital circuitry
• PD is a passive device having no gain
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DIGITAL COMMUNICATION SYSTEM
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DIGITAL COMMUNICATION SYSTEM
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FEEDFORWARD LINEARIZER
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FEEDFORWARD LINEARIZER
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DIGITAL PREDISTORTION
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ADAPTIVE DIGITAL PREDISTORTION
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ADAPTIVE DIGITAL PREDISTORTION AT IF
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Quad ModO
C
IPre Distorter O
C
I
BPFMicro ControllerF1,F2
Adaptation Algorithm
I.I^2
PA
Input
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ADAPTIVE DIGITAL PREDISTORTION AT BASEBAND
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ADAPTIVE DIGITAL PREDISTORTION AT BASEBAND
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ADAPTIVE DIGITAL PREDISTORTION(ADPD)
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ADPD Implementation issues • Input signal delay to compensate processing delays • Correction signal to contain multiple harmonics of baseband signal • Places stringent requirement on data converters • Digital correcting circuitry more complicated than the digital circuitry
generating the baseband signal
Presented by
Bhupinder Singh
RF SYSTEM DESIGN
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ANALOG TRANSCEIVER PARAMETERS
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a. Sensitivity (Noise floor, NF) b. Non Linear Distortion(2-Tone IMD) c. AM-AM and AM-PM distortion (1-Tone
Measurement)
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Noise Figure
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• Sources of receiver noise 1. Noise picked by antenna (Ta=290K) 2. Noise generated by the receiver . Thermal Noise -thermal agitation of bound charges
𝑽𝒏 = 𝟒𝒌𝑻𝑩𝑹 . 𝟏 𝒇 Noise present from 1Hz to 1MHz
. Available Noise Power= K𝑻𝒂B ; K=1.38∗ 𝟏𝟎−𝟐𝟑 (J/K) . Noise Power Density=K𝑻𝒂 (W/Hz)=-174dbm/Hz @RT
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Noise Figure (Contd.)
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SNR = 𝑾𝒂𝒏𝒕𝒆𝒅 𝑺𝒊𝒈𝒏𝒂𝒍 𝑷𝒐𝒘𝒆𝒓
𝑼𝒏𝒘𝒂𝒏𝒕𝒆𝒅 𝑵𝒐𝒊𝒔𝒆 𝑷𝒐𝒘𝒆𝒓
Noise Factor=𝑺𝑵𝑹 𝒂𝒕 𝑰𝒏𝒑𝒖𝒕
𝑺𝑵𝑹 𝒂𝒕 𝑶𝒖𝒕𝒑𝒖𝒕 for a linear 2-port N/W
=𝑺𝒊
𝑵𝒊
𝑺𝟎𝑵𝒐
=𝑵𝒐
𝑮 ∗𝑵𝒊
NF=10*log𝟏𝟎 𝑭
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Noise Figure of Cascade
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Equivalent Noise Temperature
𝑻𝒆= 𝑭 − 𝟏 ∗ 𝑻𝑶 ; hence
𝑭 =𝑻𝒆
𝑻𝒐+ 𝟏
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Note: Overall system noise temperature including antenna is
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1-db Compression
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Input signal power in dbm that produces 1-db compression in gain is 𝑷𝒊𝒏,𝟏𝒅𝒃=𝑷𝒐𝒖𝒕,𝟏𝒅𝒃 - 𝑮 + 𝟏𝒅𝒃 Minimum Detectable Signal (MDS) is defined as 3 db above the noise floor, given by 𝑴𝑫𝑺 = 𝑲𝑻𝒂𝐁 + 𝟑 𝐝𝐛
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Dynamic Range
77
Dynamic range is defined as the range between 1-db compression point and minimum detectable signal (MDS).
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Intermodulation Distortion
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Intermodulation Distortion (Contd.)
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Intermodulation Distortion (Contd.)
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Third order Intercept Point (TOI) . Figure of merit for intermodulation product suppression . High Intercept Point means higher suppression of undesired intermodulation
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Intermodulation Distortion (Contd.)
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TOI of cascade
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Intermodulation Distortion (Contd.)
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Example
Ans +9.1dbm
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DIGITALLY MODULATED SYSTEM
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• CCDF ACCDF curve shows how much time the signal spends at or above a given power level
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DIGITALLY MODULATED SYSTEM
84
ORIGIN OF CCDF CURVES
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DIGITALLY MODULATED SYSTEM
85
• CCDF specify the power characteristics of the signal that will be mixed, amplified and decoded in communication systems.
• Useful tool for baseband DSP Engineer to convey the signal characteristics to RF Engineer
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DIGITALLY MODULATED SYSTEM
86
• Pulse shaping can significantly effect CCDF curve
• A higher roll off factor (α) will result in lower Pk to Av power ratio compared with a lower roll off factor in a digital system
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DIGITALLY MODULATED SYSTEM
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• Compression effect displayed by CCDF curve
• Cause could be Nonlinearities of PA, Mixer or pre amplifier
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DIGITALLY MODULATED SYSTEM
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• EVM is the scalar distance between two phasor end points (magnitude of the difference vector)
• Usually expressed as the percent of the peak signal level, usually defined by the constellation’s corner states.
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WHAT IS BER?
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WHAT IS RESIDUAL BER?
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QAM MODULATION
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SYSTEM DIAGRAM
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RECEIVE PROBLEMS
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PRIMARY NOISE AND DISTORTION ELEMENTS
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PRIMARY BER INFLUENCES
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EFFECT OF SOURCE PHASE NOISE
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EFFECT OF SOURCE PHASE NOISE
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EFFECT OF SOURCE PHASE NOISE
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EFFECT OF SOURCE PHASE NOISE
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EFFECT OF SOURCE PHASE NOISE
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• Phone: +91 80 23432021 / +91 93435 10805
Contact information
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