signals and systems ec key-notes
DESCRIPTION
courtesy: Kreatryx.comTRANSCRIPT
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Manual for K-Notes
Why K-Notes?
Towards the end of preparation, a student has lost the time to revise all the chapters from his /
her class notes / standard text books. This is the reason why K-Notes is specifically intended for
Quick Revision and should not be considered as comprehensive study material.
What are K-Notes?
A 40 page or less notebook for each subject which contains all concepts covered in GATE
Curriculum in a concise manner to aid a student in final stages of his/her preparation. It is highly
useful for both the students as well as working professionals who are preparing for GATE as it
comes handy while traveling long distances.
When do I start using K-Notes?
It is highly recommended to use K-Notes in the last 2 months before GATE Exam
(November end onwards).
How do I use K-Notes?
Once you finish the entire K-Notes for a particular subject, you should practice the respective
Subject Test / Mixed Question Bag containing questions from all the Chapters to make best use
of it.
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BASIC CONCEPTS
In continuous time signals independent variable is continuous and thus these signals are
defined for a continuum of values of independent variable.
Discrete time signals are only defined at discrete times and consequently for these
signals the independent variable takes discrete set of values.
Representation of continuous time signals
We use symbol t to denote independent variable for continuous time signal.
These signals can be represented by a wave form as shown below
If possible, these can also be represented by a mathematical function like
x(t) = sin t
Representation of discrete time signal
We use symbol n to denote independent variable for discrete time signal.
These signals can be represented as a series of numbers like
x[n] = [5, 4, 5, 7, 9, 2]
Arrow indicates reference point or x [0]
If possible, we can represent the same by a function like
x[n] = sin n 4 Also these signals can be represented by a wave form as shown below
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Energy & Power Signals
Interval ,
Energy of continuous time signal
2 2
T
T
limE x t dt x t dt
T
Energy of discrete time signal
2 2
N
nn N
limE x n x n
T
Power of continuous time signals
2
T
T
lim 1P x t dt
T 2T
Power of discrete time signals
2
N
n N
lim 1P x n
N 2N 1
Signals having non-zero (finite) power and infinite energy are called as Power Signals.
ex. x(t) = sint
Signals having finite (non-zero) energy and zero power are called as Energy Signals.
ex. x[n] = [1, 2, 3, 4]
The bounded signal radiate finite energy and periodic signal radiate finite average
power.
Even & Odd signals
A signal is said to be even if it satisfies the condition
x(t) = x (t) or x [n] = x[n]
A signal is said to be odd if it satisfies the condition
x(t) = x(t) or x [n] = x[n]
Any signal (even those which are neither odd nor even) can be broken into odd & even
parts
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Odd Part
0
x t x tx t
2 ;
0
x n x nx n
2
Even Part
ex t x t
x t2
;
e
x n x nx n
2
Periodic and Aperiodic Signals
A signal is said to be periodic with period T or N if
x(t + T) = x(t)
x[n + N] = x[n]
Otherwise, the signals are said to be aperiodic.
Classification of systems
(i) Linear & Non-Linear Systems
For Linearity
if 1 1x t y t
2 2x t y t
then, this condition must be true
1 1 2 2 1 1 2 2x t x t y t y t
Example : y(t) = t x (t) is linear
y[n] = 2x [n] + 3 is non-linear
(ii) Time Invariant & Time-variant Systems
For system to be time-invariant the
following condition must hold true
x(t - ) y(t )
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It means that following two realizations must be equivalent
The simplest way to verify this is to check the coefficient of t inside x(t)
eg. y(t) = tx(t) is time invariant
but y(t) = tx(2t) is time variant as coefficient of t in side x(t) is not 1
Otherwise, you need to verify the system equivalence shown above.
(iii) Causal & Non-causal Systems
The output should depend only on present & past values of input.
h t 0 V t 0
For discrete time system
h[n] = 0 V n < 0
(iv) Stable & Unstable Systems
Every Bounded input should produce a bounded output.
K
DT : h k
; CT : h d
(v) LTI systems with or without memory
The output at any time should depend only on value of input at the same time.
For discrete time system
h[n] = 0 V n 0
h[n] = k [n]
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For continuous time system
h(t) = 0 V t 0
h [t] = k [t]
(vi) Invertible Systems
The system is invertible if there exists h1(t) such that
Thus h(t) * h1(t) = t
For discrete time, h[n] * h1[n] = n
Shifting and Scaling operations
Shifting
Delay
if
shift the waveform right by the amount of delay
Advance
if
shift the waveform left by the amount of advance
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Scaling
Compression
if
Replace upper & lower limit by original limit divided by compression factor
Expansion
if
Replace upper & lower limit by original limit multiplied by expansion factor.
Note : If both scaling and shifting are given in the question .
Ex. x(3t-2)
-
1. shift the waveform right by the amount of delay
2. Replace upper & lower limit by original limit divided by compression factor
This method is applicable for both continuous and discrete time signal.
LTI system (Linear Time Invariant Systems)
Any continuous time or discrete time system can be represented in terms of impulses.
x t x t d
k
x[n] x k n k
LTI systems are characterized on the basis of Impulse Response h(t) or h[n]
The response of a system with impulse as an input is called as impulse response.
Due to time invariance property of LTI system
if n h n
n k h n k
since
K
x n x k n k
k
y n x k h n k x n * h n
= convolution sum
for continuous time domain
k
y t x h t x t * h t
= convolution integral
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The condition for causality of system then becomes
h[n] =0 V n < 0 ; h(t) = 0 V t < 0
Calculating convolution sum
Suppose x [n] = u[n]
h[n] = [1, 2, 5, 7, 9]
Draw plots of both x[n] & h[n]
Flip either x[n] or h[n] about y-axis
Here, we flip x[n]
For calculating y[n], shift x[k] to right by amount n
For y[0]
The only overlapping between the two is at k = 0, 1, 2
y [0] = x[0] h [0] + x [1] h [1] + x [2] h [2]
= 1 x 5 + 1 x 2 + 1 x 1
= 8
For y [1]
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y [1] = x [0] h [1] + x [1] h [0] + x [2] h [1] + x [3] h [2]
= 1 x 7 + 1 x 5 + 1 x 1 x 1 x 2 = 15
Similarly, we can calculate all values of y[n]
y[n] = [2, 3, 8, 15, 24, 24..]
Calculating Convolution Integral
Assume x (t) = u (t)
h (t) =
Step 1
Flip either x(t) or h(t)
Here, we flip h(t)
Step 2
Shift h( ) by amount t to the right to calculate y(t) by calculating overlapping between
h t & x
Overlapping area
=
0
1 t
1.1d 1 t
if t < 1
so, overlapping area = 0
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if t > 1
overlapping area = 2
y (t) is shown in adjoining figure:
Properties of Convolution Sum
1) Commutative Property
x[n] * h[n] = h[n] * x[n]
2) Distributive Property
y1[n] = x[n] * h1[n]
y2[n] = x[n] * h2[n]
y [n] = y1[n] + y2[n] = x[n] * h1[n] + x2[n]*h2[n]
= x[n] * { h1[n] + h2[n] }
3) Associative Property
{x[n] * h1[n] }* h2[n] = { x[n]* h2[n] } * h1 [n]
Same properties will apply for continuous time domain for convolution integral.
Parallel & Cascade structure of LTI systems
Parallel:
y[n] = x[n] * [h1 [n] + h2 [n]]
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Cascade:
y[n] = x[n] * ([h1 [n] + h2 [n]])
Frequency Response
The frequency response of any LTI system is given by its Fourier Transform.
DT: jw jwnn
H e h n e
CT: jwtH jw h t e dt
Group delay & Phase delay
Assuming transfer function of system is H(s)
input is x(t)= jwt
e
Output: j wjwt jwt
H jw e H jw e e
= wt wj
H jw e
w Arg H jw
Group Delay,
g
d ww
dw
Phase Delay, w
ww
Continuous Time Fourier series
Fourier states that any periodic signal can be represented by a set of complex exponential
signals provided that it satisfies Drichlet Conditions.
Drichlet conditions
(i) Over any period x(t) is absolutely integrable
i.e., T
0
x t dt
(ii) In a finite time interval, x(t) has a finite number of maxima & minima
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(iii) It should have finite number of discontinuities in the given interval
Note : for distortion less transmission of the of a signal with some finite frequency content
through a continuous time LTI system , the frequency response of the system must satisfy these
two conditions.
1. The magnitude response H( j ) must be constant for all frequencies of interest ;
that is, we must have
H( j ) C
For some constant C
2. For the same frequencies of interest, the phase response arg H( j ) must be linear in frequency, with slope to and intercept zero ; that is, we must have
oarg H( j ) t
Fourier series as generally expressed in 2 forms.
Trigonometric
Exponential
Trigonometric Fourier Series
Analysis equations
T
00
1a x t dt
T
0T
k0
2a x t cos k t dt
T where 0 2 T
0T
k0
2b x t sin k t dt
T
Synthesis equations
0 00 k kk - k k 0 k 0
x t a a cosk t b sink t
Exponential Fourier Series
Analysis equations
0T
jk t
k0
1C x t e dt
T
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Synthesis equations
0jk t
Kk
x t C e where 0
2T
Relation between T.F.S. and E.F.S.
0oc a
n nna jb
C2
n nna jb
C2
Important facts about Trigonometric Fourier series
(i) Any odd signal contains only sine terms in Fourier series.
(ii) Any even signal contains only cosine terms in Fourier series.
(iii) For halfwave symmetric signal
Tx t x t2 Only odd harmonics are present
i.e., k = 1, 3, 5.
Properties of complex exponential Fourier Series
(i) Linearity
If kF.S.x t a
kF.S.y t b
then Ax (t) + By (t) F.S. A
ka + B
kb
(ii) Time-shifting
if kF.S.x t a
0 0 0 k-jk tF.S.x t t e a
where
02
T
(iii) Time-Reversal
if kF.S.x t a
kF.S.x t a
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For odd signal For even signal
x(t) = x(t) x(t) = x (t)
k k
a a
k k
a a
(iv) Time Scaling
if kF.S.x t a
kF.S.x t a
but 0
is replaced by 0 , though Fourier series coefficients remain same.
(v) Multiplication
if kF.S.x t a
kF.S.y t b
kF.S.z t x t y t c
pk k pP
C b a
= convolution sum
(vi) Parsevals Relation
Energy in time domain = Energy frequency Domain
22
kkT
1x t dt a
T
where kF.S.x t a
Discrete Time Fourier series
For a discrete-time signal, with period N the following equations are used for Fourier
series.
Analysis equations
N
k
2j KnNC x n e
0
2N
0N
k
j KnC x n e
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Synthesis equations
0N
K
j Knx n C e
The properties of Fourier series coefficients are same as continuous time Fourier series
with one additional property.
K N KC C
That is, Fourier series coefficients are periodic
IMPORTANT DUALITY
A signal discrete in one domain is periodic in other domain & vice versa.
Example: For continuous Time Fourier Series, x (t) is periodic in time domain & hence Fourier
Series exists where coefficients exist for frequency integral multiple of 0
" " & hence is discrete.
Fourier Transform
Fourier series exists only for periodic signals, Fourier series converges to Fourier Transform
which is continuous as compared to Fourier series which is discrete.
Continuous Time Fourier Transform
Analysis equation
jwtX jw x t e dt
Synthesis equation
jwt1
x t x jw e dw2
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Properties of Continuous Time Fourier Transform
Signal Fourier Transform
x(t) X(jw)
y(t) Y(jw)
Ax(t)+By(t) AX(jw)+BY(jw)
x(t-t0)
x*(t) X*(-w)
x(-t) X(-w)
x(at)
x(t)*y(t) X(jw)Y(jw)
jwX(jw)
x(t)y(t)
tx(t)
Ev{x(t)} Re{X(jw)}
Od{x(t)} jIm{X(jw)}
X(t) 2x(-w)
X(w-w0)
Parsevals Relation
2 21
x t x w dw2
0j te X w
jw1X
a a
dx(t)
dt
1X(w) * Y(w)
2
t
x d 1
X jw X 0 wjw
d
j X jwdw
0j te x t
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Some common Fourier Transform Pairs
Signal Fourier Transform
0jkw t
kK
a e
0kk
2 a k
0jkw te
02
cos 0w t
0 0
sin 0w t 0 0j
1 2
n
t nT
K
2 2 k
T T
1
1
1, t Tx t
0, t T
12sin T
(sin wt)/t
1, wx
0, w
t 1
u(t)
1
j
0t t 0j te
ate u t ,Re a 0 1a j
Discrete Time Fourier Transform
Analysis equation
j j nn
X e x n e
Synthesis Equation
2
j j n1x n X e e d
2
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Properties of Discrete Time Fourier Transform
Signal Fourier Transform
x[n]
y[n]
X periodic with
period 2Y
ax[n] + by [n] aX bY
0x n n
0j ne X
x*[n] X *
0j n
e x n
0X x [n] X
k
x n | k , if n is multiple of k x n
0, is n is not multiple of k
X k
x [n] * y [n]
X Y
n x [n]
dxj
d
Ev x n Re {X( )}
Od {x [n]} j Im {X( )}
Parsevals Relation
2 2
n 2
1x n X d
2
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Some common Fourier Transform Pairs
Signal Fourier Transform
k
2jk n
N
K N
a e
kk
2 k2 a
N
0j ne
02 2
cos 0n 0 02 2
0sin n 0 02 2j
x [n] = 1 2 2
1
1
1, n N
x n N0, n N , n
2
and x [n + N] = x [n]
kk
2 k2 a
N
k
n kN
k
2 2 k
N N
11
1, n Nx n
0, n N
1
1sin N2
sin2
sinWn W Wnsinc
n
1, 0 Wx
0, W <
0n n
0j ne
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Laplace Transform
Laplace Transform is more general than Fourier Transform but can only be computed in
Region of Convergence (ROC), so it cannot be computed V s
ROC = t
S jw; such that
x t e dt
Laplace transform becomes Fourier transform for 0 , if it lies in ROC.
Analysis Equations
for bilateral Laplace Transform
H(s) = sth t e dt
for unilateral Laplace Transform
H(s) = st
0
h t e dt
Synthesis Equation
x(t) = j
st
j
1x s e ds
2 j
Properties of ROC
(i) ROC consists of a collection of lines parallel to jwaxis in splane.
such that
tx t e dt
(ii) If X (s) is rational, then ROC does not contain any poles.
(iii) If x(t) is of finite duration & absolutely integrable, then ROC is entire s-plane.
(iv) If x(t) is right sided signal (i.e., it is zero before some time) and if Re(s) = 0
is in the
ROC, then all values of s for which Re(s) > 0
are also in ROC.
(v) If x(t) is left sided, (i.e., if it is zero after some time), and if Re (s) = 0
is in ROC, then
all values of s for which Re(s) < 0
are also in ROC.
(vi) If x(t) is twosided signal and if the line Re (S) = 0
is in ROC, then the ROC consists
of a strip in splane include the line Re (S) = 0
(vii) If X(s) is rational, and
x(t) is right sided signal, then ROC is right of right most pole.
x(t) is left sided signal, then ROC is left of left most pole.
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Properties of Laplace Transform
Signal Transform ROC
x(t) X(s) R
x1(t)
X1(s)
R1
x2(t) X2(s)
R2
ax1(t) + bx2(t) aX1(s) + bX2(s)
At least R1 R2
0x t t 0st
e X s
R
0s te x t 0X s s Shifted version R [i.e., s is in ROC if 0s s is in R]
x (at)
1 sX
a a
Scaled ROC i.e., s is ROC if
sa is in R
1 2x t * x t 1 2X s X s At least R1 R2
d
x tdt
sX s At least R
tx(t)
dx s
ds
R
t
x d
1
X ss
At least R
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Some common Laplace Transform Pairs
Signal Transform ROC
t 1 All s
u(t) 1s
Re {s} > 0
u(t) 1s
Re {s} < 0
n 1tu t
n 1 !
n1
s Re {s} > 0
n 1tu t
n 1 !
n1
s Re {s} < 0
ate u t 1s a
Re {s} > a
- ate u t 1s a
Re {s} < a
n 1att e u t
n 1 !
n
1
s a
Re {s} < a
n 1att e u t
n 1 !
n
1
s a
Re {s} > a
t T sTe All s
0cos t u t
02 2
s
s
Re {s} > 0
0sin t u t
0
0
2 2s
Re {s} > 0
at 0e cos t u t
02 2
s a
s a
Re {s} > a
at 0e sin t u t
0
0
2 2s a
Re {s} > a
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Initial and Final Value Theorem
limx 0 sX s initial value
s
limx s X s
s 0 Final value, first stability should be ensured, else final value does
not exist.
Analysis of LTI system using Laplace Transform
Stability
h t dt
; ROC of H(s) should include 0 .
Causality
h(t) = 0, t < 0 i.e., right sided signal
ROC should be right sided
ROC should include Right half plane.
but converse is not true.
Z Transform
It is generalization of Discrete Time Fourier Transform
Analysis Equation
k
k
H z h k z
Synthesis Equation
n 11h[n] H z z dz2 j
Indicates integration around counter clockwise circular contour centered at origin
& with radius r.
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ROC for Z-Transform
Z Transform also exists only inside ROC
nn
x n r
is the condition for ROC.
Mapping from s-plane from zplane
The jw-axis is mapped to unit circle in zplane.
Right Half plane is mapped to exterior of unit circle.
Left Half plane is mapped to interior of unit circle.
Properties of ROC
(i) The ROC x(z) consists of a ring in the z plane centered about the origin.
(ii) The ROC does not contain any poles.
(iii) If x[n] is of finite duration, then ROC is the entire z plane except possibility at z = 0
and/or z =
(iv) If x[n] is a right sided sequence and if the circle, | z | = r0 is in the ROC, then all finite
values of z, for which | z | > r0 will also be in ROC.
(v) If x[n] is a left sided sequence, and the circle | z | = r0 is in ROC, then all finite value of
z, for which 0 < | z | < r0 will be in ROC.
(vi) If x[n] is two sided sequence and if circle | z | = r0 is in the ROC. Then ROC will consist
of a ring in z-plane which consist of ring | z | = r0.
(vii) If X (z) is rational and
x[n] is right sided than ROC is outside of outer most pole.
x[n] is left sided then ROC is inside of inner most pole.
(viii) If x[n] is causal, ROC includes z = provided x[n] = 0, n < 0.
If x [n] is anti causal, ROC includes z = 0 provided x [n] = 0, n > 0.
(ix) A causal LTI system with rational system function is stable if all poles inside the unit
circle that is have magnitude, | z | < 1.
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Properties of zTransform
Signal Transform ROC
x[n] X(z) xR
1x n 1X z 1R
2x n 2X z 2R
1 2ax n bx n 1 2aX z bX z At least R1 R2
0x n n
0nz X z
Rx with addition or
deletion of origin
0j n
e x n
0jX e z xR
0nz x n
0
zXz
x0z R
x[n] 1X z 1 xz s.t z R
x r , n=rk
w n0, n rk for some r
kX z 1k1k
x xR i.e., z s.t z R
21x n * x n 1 2X z X z At least R1 R2
nx[n] zdX zdz
Rx except addition or
deletion of zero
n
k
x k 1
1X z
1 z
xR z 1
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Some common Z Transform pairs
Signal Transform ROC
n 1 All z
u n 1
1
1 z
| z | > 1
u n 1 1
1
1 z
| z | < 1
n m mz All z except 0 (if m > 0) or (if m < 0)
na u n 1
1
1 az
| z | > | a |
na u n 1 1
1
1 az
| z | < | a |
nna u n
1
21
az
1 az
| z | > | a |
nna u n 1
1
21
az
1 az
| z | < | a |
Initial & Final value Theorem
lim
x 0 X zz
Initial value
lim 1x 1 X z
zz 1 Final value
In z transform also, stability must be verified before using final value theorem.
Sampling
Continuous Discrete Time
Time signal signal
Nyquist Sampling Theorem
It states that if sampling frequency is greater than twice the maximum frequency in the
-
signal for the signal to be recovered from its samples.
MS
w 2w
Note: For this condition signal spectrum should be centered around y-axis.
Band-pass Sampling Theorem
If the signal spectrum is band-pass which means it has minimum & maximum frequency
Lf = lower frequency ; uf = upper frequency
u
u L
fK ,where
f f indicates Greatest Integer function
uS
2fw
K
px (t) = x(t) p(t)
n
p t t nT
T = sampling interval ; px t Sampled signal
x(t) = continuous time signal
pn
x t x t t nT
P1
X w X w *P w2
sk
2P w w kw
T
sPk
1X w X w kw
T
; s2
wT
The spectrum of sampled signal is just repetition of actual spectrum at integral multiples
of sw .
If s Mw 2w , adjacent samples of spectrum overlap, called as aliasing.
Discrete Fourier Transform
DFT of n point sequence is given by:
Analysis equation:
N 1
n 0
j2 kn
NX k x n .e , k = 0, 1, 2., N1
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Synthesis equation:
N 1
K 0
j2 kn
N1x n X k eN
, n = 0, 1, 2..., N 1
Each point of DFT require N complex multiplications and (N 1) complex additions.
Therefore, N point DFT will required N2 complex multiplications and N (N 1) complex
additions.
Properties of DFT
Sequence Transform
x[n] X(k)
x1[n] X1[k]
x2[n] X2[k]
x[n + N] = x[n] X(K+N)= X(k)
2 21 1a x n a x n 2 21 1a x k a x k
N 1
N1 2n 0
x n x m n
Where 2 2Nx m n x N m N
21x k x k
Nx n x N n X(N k)
Nx n 2 kj
NX K e
2 nj
NX n e
NX K
x*(n) X*(N k)
1 2x n x n N1 21
X K x kN
Circular convolution of
2 DFT sequences
Parsevals Relation
N 1 N 1
2 2
n 0 K 0
1x n x k
N
Fast Fourier Transform (FFT) Algorithms
These are the algorithms for computing DFT when the size N is a power of 2 or when it is
a power of 4.
Direct computation of DFT is inefficient because it does not exploit the properties of
symmetry and periodicity of the phase factor, 2j
NN
W e
-
Symmetry property :
NK+
2 KN N
W W
Periodicity property :
K+N KN N
W W
DFT can be expressed as :
N 1
R R In 0
2 kn 2 knX K x n cos x n sin
N N
N 1
I R In 0
2 kn 2 knX K x n sin x n cos
N N
No. of operations required for direct computation of DFT
1) 22N evolutions of trigonometric functions.
2) 24N Real multiplications.
3) 4N (N 1) real additions.
Radix 2 FFT algorithm
There are two types of FFT algorithm:
1) Decimation in time.
2) Decimation in frequency.
Radix 2 algorithm can be implemented over N point DFT sequence if N = n2 .
We divide the given time sequence by 2 till we get the prime factor.
We split the Npoint data sequence into two N
2 point data sequences 1f n and 2f n
corresponding to even numbered and numbered samples of x(n).
NN 1
nk
n 0
X K x n W
, K = 0, 1, ,N 1.
N Nnk nk
n even n odd
x n W x n W
By substituting n = 2r for n even and n = 2r + 1 for n odd,
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N N
N N1 12 2
2r 1k2rk
r 0 r 0
X k x 2r W x 2r 1 W
=
N N NN N1 1
2 2rk rk2 2 2
r 0 r 0
x 2r W W x 2r 1 W
But N2
N2
W W .
N
j22 N2 j
N2 2N
2
W e e W
N N1 1
2 2
N N2 2
rk rkN
r 0 r 0
kX k x 2r W W x 2r 1 W
=
N2
1 2
G K W H K
f k f k
, k = 0, 1, , N 1.
Now, computation of X[k] requires 2 2N N N N
22 2 2 2
complex multiplications.
We can further decimate 1f n and 2f n in time. Thus 1f n would result in two N
4
point sequences. 2f n decimation by 2 would also result in two N
4 point sequence.
We can deduce finally that total number of complex multiplication is reduced to
2
Nlog N
2 and the number of complex additions to N
2log N .
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FFT computation for 8-point DFT
Order of input is bit reversed, due to decimating twice in time domain.
Number of butterflies in N
2 per stage.
Number of stage is2
log N .
Butterfly computation.
Decimation in frequency
We split the DFT formula into two summations, one of which involves the sum over the first N
2
data points and the second sum involves the last N
2 data points.
-
Thus,
N1
N 12Kn Kn
N
2
N Nn 0 n
X k x n W x n W
N N1 Nk2 2
Kn Kn2
0
1
N N Nn 0 n
NX k x n .W W x n W
2
Since
2 NkNk jN 2 kj k2
NW e e 1
Therefore,
N1
2Knk
Nn 0
Nx k x n 1 x n W
2
Now, divide X(k) into even and odd numbered samples.
N1
2KnN
2n 0
NX 2k x n x n W
2, k = 0, 1, .
N1
2 .
n KnN
2
N1
2
n 0N
NX 2k 1 x n x n W W
2 , k = 0,1, ,
N1
2 .
Total number of complex multiplications are2
Nlog N
2.
Total Number of complex addition are 2
Nlog N .
Decimation in frequency for N = 8 FFT algorithm
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Note :
1) Order of input is normal while order of output is bit reversed.
2) Number of stages is 2
log N .
3) Number of butterflies is N
2 for stage.
Butterfly computation for decimation in frequency.
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