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MAE140 Linear Circuits 132
s-Domain Circuit Analysis
Operate directly in the s-domain with capacitors, inductors and resistors Key feature – linearity – is preserved Ccts described by ODEs and their ICs
Order equals number of C plus number of L
Element-by-element and source transformation Nodal or mesh analysis for s-domain cct variables Solution via Inverse Laplace Transform
Why? Easier than ODEs
Easier to perform engineering design Frequency response ideas - filtering
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MAE140 Linear Circuits 133
Element Transformations
Voltage source Time domain
v(t) =vS(t) i(t) = depends on cct Transform domain
V(s) =VS(s)=L(vS(t)) I(s) = L(i(t)) depends on cct
Current source
I(s) =L(iS(t)) V(s) = L(v(t)) depends on cct
+ _
i(t)
vS
iS
v(t)
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MAE140 Linear Circuits 134
Element Transformations contd
Controlled sources
Short cct, open cct, OpAmp relations
Sources and active devices behave identically Constraints expressed between transformed variables
This all hinges on uniqueness of Laplace Transforms and linearity
)()()()()()()()()()()()()()()()(
2121
2121
2121
2121
sgVsItgvtisrIsVtritvsIsItitisVsVtvtv
=⇔=
=⇔=
=⇔=
=⇔=
ββ
µµ
)()()()(0)(0)(0)(0)(
sVsVtvtvsItisVtv
PNPN
OCOC
SCSC
=⇔=
=⇔=
=⇔=
![Page 4: s-Domain Circuit Analysisnodes.ucsd.edu/.../140_LinearCircuits/data/6sdomain.pdfMAE140 Linear Circuits 132 s-Domain Circuit Analysis Operate directly in the s-domain with capacitors,](https://reader036.vdocument.in/reader036/viewer/2022081517/5fc17b48a01f3a4cf0240512/html5/thumbnails/4.jpg)
MAE140 Linear Circuits 135
Element Transformations contd
Resistors
Capacitors
Inductors
)()()()()()()()(sGVsIsRIsVtGvtitRitv
RRRR
RRRR==
==
iR
vR
sisV
sLsILissLIsV
idvL
tidttdiLtv
LLLLLL
tLLL
LL
)0()(1)()0()()(
)0()(1)()()(0
+=−=
+== ∫ ττ
R s Y R s Z R R 1 ) ( ) ( = =
sC s Y sC s Z C C = = ) ( 1 ) (
sL s Y sL s Z L L 1 ) ( ) ( = =
vC
iC
vL
iL + + +
svsI
sCsVCvssCVsI
vdiC
tvdttdvCti
CCCCCC
CtCC
CC
)0()(1)()0()()(
)0()(1)()()(0
+=−−=
+== ∫ ττ
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MAE140 Linear Circuits 136
Element Transformations contd Resistor
Capacitor
Note the source transformation rules apply!
IR(s)
VR(s)
+
-
vR(t)
+
-
vC(t)
+
-
iR(t)
iC(t)
R R
C sC1
)0(CCvVC(s)
+
-
IC(s)
VC(s)
+
-
IC(s)
+ _ s
vC )0(
sC1
) ( ) ( s RI s V R R =
s v s I
sC s V Cv s sCV s I C C C C C C
) 0 ( ) ( 1 ) ( ) 0 ( ) ( ) ( + = - - =
![Page 6: s-Domain Circuit Analysisnodes.ucsd.edu/.../140_LinearCircuits/data/6sdomain.pdfMAE140 Linear Circuits 132 s-Domain Circuit Analysis Operate directly in the s-domain with capacitors,](https://reader036.vdocument.in/reader036/viewer/2022081517/5fc17b48a01f3a4cf0240512/html5/thumbnails/6.jpg)
MAE140 Linear Circuits 137
Element Transformations contd
Inductors s
i s V sL s I Li s sLI s V L
L L L L L ) 0 ( ) ( 1 ) ( ) 0 ( ) ( ) ( + = - =
iL(t) + _ vL(t)
-
+ sL
LiL(0)
IL(s) +
VL(s)
-
IL(s)
VL(s) +
-
sL siL )0(
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MAE140 Linear Circuits 138
Example 10-1 T&R p 456
RC cct behavior Switch in place since t=-∞, closed at t=0. Solve for vC(t).
R
VA
t=0
C
R
sC1
)0(CCv
I2(s)
I1(s)
vC +
-
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MAE140 Linear Circuits 139
Example 10-1 T&R p 456
RC cct behavior Switch in place since t=-∞, closed at t=0. Solve for vC(t).
Initial conditions s-domain solution using nodal analysis
t-domain solution via inverse Laplace transform
R
VA
t=0
C
R
sC1
)0(CCv
I2(s)
I1(s)
vC +
-
)(1)()()()( 21 ssCV
sC
sVsIRsVsI C
CC ===
AC Vv =)0(
)()(1)( tueVtv
RCs
VsV RCt
AcA
C−
=+
=
![Page 9: s-Domain Circuit Analysisnodes.ucsd.edu/.../140_LinearCircuits/data/6sdomain.pdfMAE140 Linear Circuits 132 s-Domain Circuit Analysis Operate directly in the s-domain with capacitors,](https://reader036.vdocument.in/reader036/viewer/2022081517/5fc17b48a01f3a4cf0240512/html5/thumbnails/9.jpg)
MAE140 Linear Circuits 140
Example 10-2 T&R p 457
Solve for i(t)
+ _
R
VAu(t) L i(t) + _
+ _
R
sL I(s) sVA
LiL(0)
)(sVL
+
-
![Page 10: s-Domain Circuit Analysisnodes.ucsd.edu/.../140_LinearCircuits/data/6sdomain.pdfMAE140 Linear Circuits 132 s-Domain Circuit Analysis Operate directly in the s-domain with capacitors,](https://reader036.vdocument.in/reader036/viewer/2022081517/5fc17b48a01f3a4cf0240512/html5/thumbnails/10.jpg)
MAE140 Linear Circuits 141
Example 10-2 T&R p 457
Solve for i(t)
KVL around loop
Solve
Invert
+ _
R
VAu(t) L i(t) + _
+ _
R
sL I(s) sVA
LiL(0)
)(sVL
+
-
0)0()()( =++− LA LisIsLRsV
€
i(t) =VAR−VARe−RtL + iL (0)e
−Rt L
u(t) Amps
€
I(s) =VA
Ls s+ RL( )
+iL (0)s+ RL
=VA
Rs
+iL (0) −
VAR
s+ RL
![Page 11: s-Domain Circuit Analysisnodes.ucsd.edu/.../140_LinearCircuits/data/6sdomain.pdfMAE140 Linear Circuits 132 s-Domain Circuit Analysis Operate directly in the s-domain with capacitors,](https://reader036.vdocument.in/reader036/viewer/2022081517/5fc17b48a01f3a4cf0240512/html5/thumbnails/11.jpg)
MAE140 Linear Circuits 142
Impedance and Admittance
Impedance is the s-domain proportionality factor relating the transform of the voltage across a two-terminal element to the transform of the current through the element with all initial conditions zero
Admittance is the s-domain proportionality factor relating the transform of the current through a two-terminal element to the transform of the voltage across the element with initial conditions zero
Impedance is like resistance Admittance is like conductance
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MAE140 Linear Circuits 143
Circuit Analysis in s-Domain
Basic rules The equivalent impedance Zeq(s) of two impedances Z1(s)
and Z2(s) in series is
Same current flows
The equivalent admittance Yeq(s) of two admittances Y1(s) and Y2(s) in parallel is
Same voltage
)()()( 21 sZsZsZeq +=
I(s)
V(s) Z2
Z1 +
-
( ) ( )sIsZsIsZsIsZsV eq )()()()()( 21 =+=
)()()( 21 sYsYsYeq +=
I(s)
V(s) Y1
+
- Y2 )()()()()()()( 21 sVsYsVsYsVsYsI eq=+=
![Page 13: s-Domain Circuit Analysisnodes.ucsd.edu/.../140_LinearCircuits/data/6sdomain.pdfMAE140 Linear Circuits 132 s-Domain Circuit Analysis Operate directly in the s-domain with capacitors,](https://reader036.vdocument.in/reader036/viewer/2022081517/5fc17b48a01f3a4cf0240512/html5/thumbnails/13.jpg)
MAE140 Linear Circuits 144
Example 10-3 T&R p 461
Find ZAB(s) and then find V2(s) by voltage division
+ _
L
v1(t) R C
A
B
v2(t) +
-
+ _
sL
V1(s) R
A
B
V2(s) +
- sC1
Ω +
+ + =
+ + = + =
1 1 1 1 ) (
2 RCs
R Ls RLCs sC
R
sL sC R sL s Z eq
)()()()()( 121
12 sV
RsLRLCsRsV
sZsZsV
eq
++=
=
![Page 14: s-Domain Circuit Analysisnodes.ucsd.edu/.../140_LinearCircuits/data/6sdomain.pdfMAE140 Linear Circuits 132 s-Domain Circuit Analysis Operate directly in the s-domain with capacitors,](https://reader036.vdocument.in/reader036/viewer/2022081517/5fc17b48a01f3a4cf0240512/html5/thumbnails/14.jpg)
MAE140 Linear Circuits 145
Superposition in s-domain ccts
The s-domain response of a cct can be found as the sum of two responses 1. The zero-input response caused by initial condition
sources with all external inputs turned off 2. The zero-state response caused by the external sources
with initial condition sources set to zero Linearity and superposition
Another subdivision of responses 1. Natural response – the general solution
Response representing the natural modes (poles) of the cct
2. Forced response – the particular solution Response containing modes due to the input
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MAE140 Linear Circuits 146
Example 10-6 T&R p 466
The switch has been open for a long time and is closed at t=0.
Find the zero-state and zero-input components of V2(s) Find v(t) for IA=1mA, L=2H, R=1.5KΩ, C=1/6 µF
IA
v(t)
t=0
R C L
+
-
V(s) R sL
+
- sI A
sC1
RCIA
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MAE140 Linear Circuits 147
Example 10-6 T&R p 466
The switch has been open for a long time and is closed at t=0.
Find the zero-state and zero-input components of V2(s) Find v(t) for IA=1mA, L=2H, R=1.5KΩ, C=1/6 µF
IA
v(t)
t=0
R C L
+
-
V(s) R sL
+
- sI A
sC1
RCIA
R Ls RLCs RLs
sC R sL
s Z eq + +
= + +
= 2 1 1
1 ) (
LCs
RCs
sRIRCIsZsV
LCs
RCs
CI
sIsZsV
AAeqzi
AA
eqzs
11)()(
11)()(
2
2
++==
++==
![Page 17: s-Domain Circuit Analysisnodes.ucsd.edu/.../140_LinearCircuits/data/6sdomain.pdfMAE140 Linear Circuits 132 s-Domain Circuit Analysis Operate directly in the s-domain with capacitors,](https://reader036.vdocument.in/reader036/viewer/2022081517/5fc17b48a01f3a4cf0240512/html5/thumbnails/17.jpg)
MAE140 Linear Circuits 148
Example 10-6 contd
Substitute values
LCs
RCs
sRIRCIsZsV
LCs
RCs
CI
sIsZsV
AAeqzi
AA
eqzs
11)()(
11)()(
2
2
++==
++==
€
Vzs(s) =6000
(s+1000)(s+ 3000)=
3s+1000
+−3
s+ 3000vzs(t) = 3e−1000t − 3e−3000t[ ]u(t)
€
Vzi (s) =1.5s
(s+1000)(s+ 3000)=
−0.75s+1000
+2.25
s+ 3000vzi (t) = −0.75e−1000t + 2.25e−3000t[ ]u(t)
V(s) R sL
+
- sI A
sC1
RCIA
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MAE140 Linear Circuits 149
Example
Formulate node voltage equations in s-domain
+ _
R1
v1(t) + -
R2 C2
C1 R3 vx(t) +
- µvx(t) v2(t)
+
-
![Page 19: s-Domain Circuit Analysisnodes.ucsd.edu/.../140_LinearCircuits/data/6sdomain.pdfMAE140 Linear Circuits 132 s-Domain Circuit Analysis Operate directly in the s-domain with capacitors,](https://reader036.vdocument.in/reader036/viewer/2022081517/5fc17b48a01f3a4cf0240512/html5/thumbnails/19.jpg)
MAE140 Linear Circuits 150
Example
Formulate node voltage equations in s-domain
+ _
R1
v1(t) + -
R2 C2
C1 R3 vx(t) +
- µvx(t) v2(t)
+
-
+ _
R1
V1(s) + -
R2
C2vC2(0)
R3 Vx(s) +
- µVx(s) V2(s)
+
- 1
1sC
C1vC1(0) 2
1sC
A B C D
![Page 20: s-Domain Circuit Analysisnodes.ucsd.edu/.../140_LinearCircuits/data/6sdomain.pdfMAE140 Linear Circuits 132 s-Domain Circuit Analysis Operate directly in the s-domain with capacitors,](https://reader036.vdocument.in/reader036/viewer/2022081517/5fc17b48a01f3a4cf0240512/html5/thumbnails/20.jpg)
MAE140 Linear Circuits 151
Example contd
Node A: Node D:
Node B:
Node C:
+ _
R1
V1(s) + -
R2
C2vC2(0)
R3 Vx(s) +
- µVx(s) V2(s)
+
- 1
1sC
C1vC1(0) 2
1sC
A B C D
€
VB (s) −VA (s)R1
+VB (s) −VD (s)
R2+VB (s)1sC1
+VB (s) −VC (s)
1sC2
−C1vC1(0) −C2vC2(0) = 0
)()( 1 sVsVA = )()()( sVsVsV CxD µµ ==
€
−sC2VB (s) + sC2 +G3[ ]VC (s) = −C2vC2(0)
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MAE140 Linear Circuits 152
Example
Find vO(t) when vS(t) is a unit step u(t) and vC(0)=0
Convert to s-domain
+ _ R1
vS(t) + - C R2 vO(t) +
A B C D
![Page 22: s-Domain Circuit Analysisnodes.ucsd.edu/.../140_LinearCircuits/data/6sdomain.pdfMAE140 Linear Circuits 132 s-Domain Circuit Analysis Operate directly in the s-domain with capacitors,](https://reader036.vdocument.in/reader036/viewer/2022081517/5fc17b48a01f3a4cf0240512/html5/thumbnails/22.jpg)
MAE140 Linear Circuits 153
Example
Find vO(t) when vS(t) is a unit step u(t) and vC(0)=0
Convert to s-domain
+ _ R1
vS(t) + - C R2 vO(t) +
A B C D
+ _
R1
VS(s) + -
R2
VO(s) +
sC1
CvC(0)
VA(s) VB(s) VC(s) VD(s)
![Page 23: s-Domain Circuit Analysisnodes.ucsd.edu/.../140_LinearCircuits/data/6sdomain.pdfMAE140 Linear Circuits 132 s-Domain Circuit Analysis Operate directly in the s-domain with capacitors,](https://reader036.vdocument.in/reader036/viewer/2022081517/5fc17b48a01f3a4cf0240512/html5/thumbnails/23.jpg)
MAE140 Linear Circuits 154
Example
Nodal Analysis Node A: Node D: Node C: Node B: Node C KCL: Solve for VO(s)
Invert LT
+ _
R1
VS(s) + -
R2
VO(s) +
sC1
CvC(0)
VA(s) VB(s) VC(s) VD(s)
)()( sVsV SA =
)()( sVsV OD =
)0()()()( 11 CSB CvsVGsVsCG =−+
0)( =sVC
)0()()( 2 COB CvsVGssCV −=−−
€
VO(s) = −
sG1CG2
G1 + sC
VS (s) = −
R2R1×
ss+ 1
R1C
VS (s)
= −R2R1×
ss+ 1
R1C
1s
=−R2R1
×1
s+ 1R1C
) ( ) ( 1 1 2 t u e
R R t v C R
t O
- -
=
![Page 24: s-Domain Circuit Analysisnodes.ucsd.edu/.../140_LinearCircuits/data/6sdomain.pdfMAE140 Linear Circuits 132 s-Domain Circuit Analysis Operate directly in the s-domain with capacitors,](https://reader036.vdocument.in/reader036/viewer/2022081517/5fc17b48a01f3a4cf0240512/html5/thumbnails/24.jpg)
MAE140 Linear Circuits 155
Features of s-domain cct analysis
The response transform of a finite-dimensional, lumped-parameter linear cct with input being a sum of exponentials is a rational function and its inverse Laplace Transform is a sum of exponentials
The exponential modes are given by the poles of the response transform
Because the response is real, the poles are either real or occur in complex conjugate pairs
The natural modes are the zeros of the cct determinant and lead to the natural response
The forced poles are the poles of the input transform and lead to the forced response
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MAE140 Linear Circuits 156
Features of s-domain cct analysis
A cct is stable if all of its poles are located in the open left half of the complex s-plane A key property of a system Stability: the natural response dies away as t→∞ Bounded inputs yield bounded outputs
A cct composed of Rs, Cs and Ls will be at worst marginally stable With Rs in the right place it will be stable
Z(s) and Y(s) both have no poles in Re(s)>0
Impedances/admittances of RLC ccts are “Positive Real” or energy dissipating