multi-generational test plan generation and execution in
TRANSCRIPT
Multi-generational Test Plan Generation and Execution in Advanced Mixed-
Signal Controllers
by
Shruti Eravelli, B.Tech.
A Thesis
In
ELECTRICAL ENGINEERING
Submitted to the Graduate Faculty
of Texas Tech University in
Partial Fulfillment of
the Requirements for
the Degree of
MASTER OF SCIENCE
IN
ELECTRICAL ENGINEERING
Approved
Dr. Richard Gale
Chairperson of the committee
Dr. Stephen Bayne
Peggy Gordon Miller
Dean of the Graduate School
May, 2011
Copyright 2011, Shruti Eravelli
Texas Tech University, Shruti Eravelli, May 2011
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Acknowledgements
I would like to first thank my advisor Dr. Richard Gale for his guidance and motivation
all through my coursework and professional career. He constantly monitored my progress
in this project and provided good suggestions which helped me refine my work. My
sincere thanks to Dr. Stephen Bayne for his readiness to serve as an important member in
my thesis committee.
I would like to express my sincere gratitude to Daniel Kimmitt at Texas Instruments,
Tucson, AZ, for being the manager he was. He gave me clear directions and checkpoints
to keep me on track and on time. Many thanks to Mickey and Jeff for patiently helping
me break down the big problems into manageable and solvable tasks and guiding me
throughout the project. I also thank Ben for his help anytime I needed it. I extend my
gratitude to all my team members at TI for their invaluable assistance throughout the
project.
Last but definitely not the least, many thanks to my parents for their encouragement and
support without which this would not have been possible.
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Table of Contents
Acknowledgements ............................................................................................................. ii
Abstract .............................................................................................................................. vi
List of Tables .................................................................................................................... vii
List of Figures .................................................................................................................. viii
I.Analog Monitoring and Control ....................................................................................... 1
1.1 AMC Applications .................................................................................................... 1
1.2 AMC Family Comparison ......................................................................................... 1
1.3 Test/Characterization Boards .................................................................................... 4
II.Integrated Circuit Packaging ........................................................................................... 7
2.1 IC Package Types ...................................................................................................... 7
2.1.1 Through-Hole Packages ..................................................................................... 7
2.1.2 Surface Mount Packages .................................................................................... 8
2.1.3 Contactless Packages .......................................................................................... 8
2.2 Quad Flat No Leads (QFN) ..................................................................................... 12
2.3 Quad Flat Package (QFP) ........................................................................................ 13
III.Hardware Interface – Board Design ............................................................................ 15
3.1 Printed Circuit Board .............................................................................................. 15
3.2 PCB Design Workflow............................................................................................ 17
3.3 AMC 7891 Daughter Board Design ........................................................................ 19
3.4 PCB Layout ............................................................................................................. 22
3.4.1 Trace Parasitics ................................................................................................. 23
3.4.2 Grounding ......................................................................................................... 24
3.4.3 Bypass Capacitors............................................................................................. 25
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3.5 PCB Materials ......................................................................................................... 25
IV.Software Interface – Labview ...................................................................................... 28
4.1 Introduction ............................................................................................................. 28
4.2 Advantages .............................................................................................................. 29
4.3 Front Panels ............................................................................................................. 30
4.4 Code Debug ............................................................................................................. 32
V.Digital To Analog Converter Characterization ............................................................. 34
5.1 DAC Architectures .................................................................................................. 35
5.1.1 String Architecture ........................................................................................... 36
5.1.2 String DAC Advantages ................................................................................... 37
5.2 DAC Testing ........................................................................................................... 37
5.2.1 Offset Error ....................................................................................................... 38
5.2.2 Offset Error Drift .............................................................................................. 38
5.2.3 Integral Non-Linearity ...................................................................................... 38
5.2.4 Differential Non-Linearity ................................................................................ 39
5.2.5 Gain Error ......................................................................................................... 40
5.2.6 Gain Error Drift ................................................................................................ 41
5.2.7 Full Scale Error ................................................................................................. 41
5.2.8 Digital Feedthrough .......................................................................................... 41
5.2.9 Glitch Impulse .................................................................................................. 42
5.2.10 Settling Time .................................................................................................. 42
5.2.11 Slew Rate ........................................................................................................ 43
VI.Analog To Digital Converter and GPIO Characterization .......................................... 45
6.1 ADC Architectures .................................................................................................. 45
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6.1.1 Successive-Approximation Register ADC ....................................................... 45
6.2 ADC Testing ........................................................................................................... 46
6.2.1 Offset Error ....................................................................................................... 47
6.2.2 Integral Non-Linearity ...................................................................................... 48
6.2.3 Differential Non-Linearity ................................................................................ 48
6.2.4 Gain Error ......................................................................................................... 49
6.3 General Purpose Input/Output ................................................................................. 50
6.4 GPIO Results ........................................................................................................... 51
VII.Conclusion and Future Work ..................................................................................... 52
7.1 Conclusion ............................................................................................................... 52
7.2 Future Work ............................................................................................................ 52
Bibliography ..................................................................................................................... 54
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Abstract
Most integrated circuits are evolutionary. This is especially true in the realm of system-
on-a-chip (SoC) devices that combine multiple functions monolithically. Electronic
systems that begin life as an entire printed circuit board often see smaller and smaller
chip counts as designs mature. In some cases, functions will be combined into multichip
modules that co-locate separate integrated circuits in a single package to provide
additional levels of signal integrity and achieve cost reductions. This process continues
through stages that culminate in the monolithic integration of these separate chips. The
requirement to differentiate similar functions for different customers and applications
results in families of SOC’s with similar but not identical capabilities. As parametric and
functional testing become larger and larger contributors to total cost, avoiding duplication
of effort is a key factor maintaining competitive position and market share. The strategies
involved in achieving economies of scale that can be realized by recognizing the
similarities between family members while still providing for differentiation where
required is a subject of great interest currently. This work traces the development of test
capability in such a family through several generations. An approach that utilizes a
motherboard to take advantage of the similarities between family members and is
combined with specialized hardware realized in a series of daughter boards, and
differentiated software as well is described through several design iterations. Debugging
both hardware and software while looking for ways to streamline testing and further
reduce test time and cost is detailed. The result is a cost effective approach to advanced
device testing that does not compromise performance and provides for acceptable levels
of fault coverage.
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List of Tables
1.1 AMC family comparison .............................................................................................. 2
3.1 AMC 7891 mother board netlist mapping .................................................................. 20
6.1 GPIO results ................................................................................................................ 51
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List of Figures
1.1 AMC 7891 schematic ................................................................................................... 2
1.2 AMC 7824 schematic ................................................................................................... 3
1.3 AMC 7812 schematic ................................................................................................... 3
1.4 Board hierarchy ............................................................................................................. 4
1.5 AMC 7824 setup ........................................................................................................... 5
1.6 AMC 7812 setup ........................................................................................................... 5
2.1 IC package classifications ............................................................................................. 9
2.2 Through-hole mount package ..................................................................................... 10
2.3 Surface mount package ............................................................................................... 11
2.4 QFN cross-section ....................................................................................................... 13
2.5 QFP cross-section ....................................................................................................... 14
3.1 CAD-based PCB design and fabrication process........................................................ 18
3.2 AMC family mother board.......................................................................................... 19
3.3 AMC 7891 daughter board schematic capture............................................................ 22
3.4 AMC 7891 daughter board ground plane ................................................................... 24
3.5 AMC 7891 daughter board layout (layer 4 and all layers visible) .............................. 25
3.6 AMC 7891 daughter board (front and back View) ..................................................... 26
3.7 AMC 7891 setup ......................................................................................................... 26
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4.1 Example labview code ................................................................................................ 28
4.2 AMC characterization setup ....................................................................................... 29
4.3 AMC characterization labview panels ........................................................................ 31
4.4 Individual labview panels ........................................................................................... 32
5.1 Piecewise constant output of a conventional practical DAC ...................................... 34
5.2 Principal string architecture with voltage output ........................................................ 36
5.3 DAC offset error ......................................................................................................... 38
5.4 DAC integral non-linearity ......................................................................................... 39
5.5 DAC differential non-linearity .................................................................................... 40
5.6 DAC gain error ........................................................................................................... 40
5.7 DAC full scale error .................................................................................................... 41
5.8 Digital feedthrough in a DAC ..................................................................................... 42
5.9 DAC settling time measurement. ................................................................................ 43
5.10 Settling time and glitch energy ................................................................................. 43
6.1 Successive Approximation ADC Block Diagram ....................................................... 46
6.2 ADC offset error ......................................................................................................... 47
6.3 ADC integral non-linearity ......................................................................................... 48
6.4 ADC differential non-linearity .................................................................................... 49
6.5 ADC gain error ........................................................................................................... 49
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Chapter I
Analog Monitoring and Control
System-on-a-chip (SOC) refers to integrating all components of a computer or other
electronic system into a single integrated circuit (IC). It may contain digital, analog,
mixed-signal, and often radio-frequency functions – all on a single chip substrate. An
Analog Monitoring and Control or AMC also falls under the same category, with
multiple functionality combined into multichip modules that co-locate separate integrated
circuits in a single package to provide additional levels of signal integrity.
1.1 AMC Applications
AMC typically has, like the name suggests, functional blocks of data converters, both
analog to digital (ADC) and digital to analog (DAC), general purpose input/output
(GPIO), temperature sensors etc. Their system and signal integrity makes them ideal for
applications such as RF power transistor gate bias control, industrial control, data
acquisition systems, communication equipment, optical networks, automatic test
equipment and other general analog monitoring and control systems. Depending on the
needs of the circuitry, different combinations of the functional blocks of AMC can be put
together to make a custom chip for a particular application or a particular customer.
Texas Instruments’ AMC 7824, 7812 and 7891 are such examples of functionally similar
but technically different analog monitoring and control integrated circuits.
1.2 AMC Family Comparison
As clearly seen in the block diagrams, all the three AMCs are functionally very similar
with similar modules put together on a single chip. It is the combination of blocks that
differentiates one from the other. The electrical characteristics and maximum ratings also
vary based on the design. In case of a custom chip, the customer/application where the
AMC is to be used decides a lot of these factors including the kind of packaging used.
Table 1.1 describes the differences and similarities briefly.
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Table 1.1 AMC family comparison
AMC 7891 AMC 7824 AMC 7812
# of Pins 36 48 64
GPIO 12 X 8
ADC channels 8 8 16
# of DAC 4 4(5) 12
SPI 4 X 4
I2C X 2 2
Remote T Sensor X 2 2
DGND 1 3 2
AGND 2 2 4
Packaging QFN QFN, TQFP QFN
Supply AVdd, DVdd, IOVdd AVdd1. AVdd2,
AVcc, DVdd, IOVdd
AVdd1. AVdd2,
AVcc1, AVcc2,
DVdd, IOVdd
Figure 1.1 AMC 7891 schematic
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Figure 1.2 AMC 7824 schematic
Figure 1.3 AMC 7812 schematic
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1.3 Test/Characterization Boards
Every AMC is unique and each unique IC needs a unique custom board to
characterize/test it because of the difference in, for example, pin count, number of power
supplies, number of ADC and DAC channels, GPIO and temperature sensor count, etc. In
any case, creating one for each family eventually becomes a very inefficient way of
dealing with the testing process of the ICs. This is because, although the three AMC
family ICs are physically different from one another, they share a lot of common blocks,
to which level a common (mother) board can be used. The dissimilarities in the AMC
family can be taken care of by a custom (daughter) board which houses circuitry specific
to the IC. This approach saves the designers from designing the entire huge complex
circuitry again and again. Instead very limited time goes into designing the small custom
daughter board with limited circuitry, essentially only the pin connections to the
resources on the mother board. The motherboard can thus house circuitry which is
common to all the AMCs like power supplies and meter connections. All the common
switches, amplifiers and multiplexers that normally go into typical test boards for ICs can
now once and for all be placed on the motherboard and forgotten about even when a
completely new IC, AMC or not, is conceived. If in any case, there is a need for circuitry
which is not available on the motherboard, the designers always have the flexibility to
add it on the daughter board.
Figure 1.4 Board hierarchy
DUTDaughter
BoardMother Board
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Figure 1.5 AMC 7824 setup
Figure 1.6 AMC 7812 setup
Some examples of the resources available on the motherboard are:
4 analog outputs of +/- 20 V
4 analog outputs of +/- 12.5 V
+/- 15 V and 5 V
12 lines for analog measurement (netlist: ANALOG_OUT1 to ANALOG_OUT12)
8 lines for analog measurement (netlist: MONITOR1 to MONITOR8)
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Temperature sensor circuit
AMC 7891 can also share the same mother board that AMC 7824 and AMC 7812 use. Its
custom daughter board is designed using Mentor Graphics Design Capture. The kind of
socket used for housing the IC depends on the pin count, size of the IC and the kind of
packaging used. As IC speeds have increased and power supply voltages have decreased,
the function of the IC package has transitioned from that of a mechanical interconnect
which provides protection for the die from the outside environment to that of an electrical
interconnect that affects IC performance and which must be properly understood in an
electrical context. The same is discussed in chapter II.
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Chapter II
Integrated Circuit Packaging
Integrated circuit packaging is the final stage of semiconductor device fabrication per se,
followed by IC testing. In the integrated circuit industry it is called simply packaging and
sometimes semiconductor device assembly, or simply assembly. Also, sometimes it is
called encapsulation or seal. The term packaging generally comprises the steps or the
technology of mounting and interconnecting of devices (1). Although it is possible to
attach chips directly to boards, placing chips in packages enables independent testing of
packaged parts, and eases requirements on board pitch and P&P (pick-and-place)
equipment. Package attributes that are taken into consideration when choosing a package
type for a particular semiconductor device include: size, weight, lead count, power
dissipation, field operating conditions, and of course, cost.
2.1 IC Package Types
Packages can be categorized as Through Hole, Surface Mount and Contactless packages.
2.1.1 Through-Hole Packages
Through-hole packages are perhaps the most common type of IC package. Their defining
quality is one or more rows of leads (short metallic posts that conduct signals to and from
the device) designed to pass through holes on a circuit board for soldering or into an
optional socket designed to receive them. The number of leads on a through-hole package
can vary from 3 to 64 and their bodies are made from either plastics or ceramics.
Common versions of these packages have one row of leads called a "single inline
package" (SIP), two rows of leads called a "dual inline package" (DIP) or a grid
arrangement of leads called a “pin grid array” (PGA).
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2.1.2 Surface Mount Packages
Like through-hole packages, most surface mount packages have leads provided to solder
the package to a circuit board. They do not pass through holes or fit into a socket,
however. Instead, they are bent at an angle near the end to form a foot to facilitate
soldering to the surface of a circuit board; however, ball grid arrays (BGA) are the
exception to this rule. The number of leads on surface mount packages can range from 4
to 1,312 and their bodies can be constructed from ceramics, plastics, metals or a
combination of the three. Common types of surface mount packages include small outline
(SO) packages, with a single row of leads and flat packs (FP), which have leads on two or
four sides of the package.
Technically, ball grid array packages are surface mount packages; however, unlike all
other surface mounts, they do not have solderable leads in a few straight rows. Instead,
their leads are ball shaped and arranged in a grid pattern on the underside of the package.
The BGA IC is positioned on a circuit board and held against contacts on the board with
pressure from a clip or other spring mechanism. BGA packages can have from 56 to
1,312 leads and their bodies are constructed from either plastics or ceramics.
2.1.3 Contactless Packages
Contactless packages are the newest type of IC to enter widespread use. Unlike most ICs,
contactless ICs do not come into direct physical contact with a circuit board. Instead, they
are scanned to provide information to other devices wirelessly. Contactless packages
have no leads and are made only with plastic bodies. They are used heavily in
identification applications, such as those used to identify shipping units, in scannable
identification cards or surgically implanted into pets to identify them to their owners
should they be lost (2).
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Figure 2.1 IC package classifications
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Figure 2.2 Through-hole mount package
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Figure 2.3 Surface mout package
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2.2 Quad Flat No Leads (QFN)
The QFN package is a lead-less, near Chip Scale Package (CSP) with low profile (1.0mm
and less), moderate thermal dissipation and good electrical performance. It is a surface
mount plastic package with leads located at the bottom of the package. It includes an
exposed thermal pad to improve heat transfer out of the IC (into the PCB). Heat transfer
can be further facilitated by metal vias in the thermal pad. As the package size shrinks
and the lead count increases, the dimensional tolerance and positioning accuracy affects
subsequent processes. Special care must be taken when preparing for test, especially in
the test contactor cavity design and contactor pin location. Further down the process, the
PCB layout and stencil designs are critical to ensure sufficient solder coverage between
the package and the Printed Circuit Board (PCB). The small size of the exposed contacts
and the large area of exposed thermal pad make it easy for small parts to float on the pool
of molten solder under the thermal pad during assembly. This causes the parts to make no
contact to the printed circuit board pads in some instances. Due to the excellent thermal
characteristics of this mounting package, it is very hard to rework the device, as hot air
reflow typically does not offer enough heat to the thermal pad without damage to
surrounding board material or parts. Oxidation of the exposed chip contact pads after
being exposed to a reflow oven during initial assembly makes solder wetting to them
during rework quite difficult. Additionally there is no clearance for a soldering pencil to
reflow pads under the chip if touch up is desired. Sometimes contact can be made up the
sides of the QFN package contact pads, but this does not work well in practice. However,
Low standoff heights, reduced lead inductance, small size and weight coupled with
excellent thermal and electrical properties make the QFN an ideal choice for a wide range
of applications. Cell phones, PDAs, portable music and video players can significantly
benefit from this package (3).
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Figure 2.4 QFN cross-section
2.3 Quad Flat Package (QFP)
The Quad Flat Package (QFP) is a high lead count and four-sided package with lead
extending from the component body on all four sides, predominantly used to house
ASIC, logic, and processor devices. QFP components packaged in trays or on tape and
reel to protect the component lead that can be easily damaged. It is ideal for
semiconductor technologies such as ASIC, SDP, controllers, processors, gate arrays
(FPGA/PLD), SRAMS and PC chip sets. It is also particularly suitable for light-weight
portable electronics requiring broad performance, such as laptop PCs, video/audio,
telecom, cordless/RF, data transmission, office automation, disc drives and
communication boards (Ethernet, ISDN). TQFP family is a reduced body thickness
plastic package. This package type is constructed using the latest wire bonding and
molding technology to provide surface mount with a nominal body thickness of 1.0mm.
It is suitable for applications where height and weight are a critical factor. TQFP give
designers the needed low profile margin in designing and producing high performing
products such as disk drives, pagers, wireless, CATV/RF modules, radio and other
similar applications.
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Figure 2.5 QFP cross-section
Based on the type of packaging used, the IC size and pin count, the sockets are decided
for use on a printed circuit board. The procedure and workflow of PCB design is
discussed in chapter III.
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Chapter III
Hardware Interface – Board Design
3.1 Printed Circuit Board
One of the common debates in test engineering is the choice between hand-wired
prototype boards versus printed circuit boards (PCB). Hand-wired boards can be quickly
constructed from prefabricated blank prototype boards. The alternate approach is to
produce a production-worthy custom PCB version of the same board without first
building a hand-wired prototype. PCB is a component made of one or more layers of
insulating material with electrical conductors. The insulator is typically made on the base
fiber reinforced resins, ceramics, plastics, or some other dielectric materials. During
manufacturing, the portions of conductors that are not needed are etched off, leaving
printed circuits that connect electronic components. Weather a PCB is single-sided,
double-sided or multi-layered; there is a standard that provides rules for
manufacturability and quality such as requirements for material properties, criteria for
surface plating, conductor thickness, component placement, dimensioning and tolerance
rules and more. For example, the width of the circuit conductors should be chosen based
on the maximum temperature rise at the rated current and the acceptable impedance. The
spacing between the PC traces is determined by peak working voltage, the coating and
the product application. The minimum possible widths of traces and of spacing between
them are both limited by the manufacturing capabilities. The effects of non-zero trace
impedance and the coupling of signals from one circuit to another through parasitic
capacitance and radio transmission should also be considered. Thus, good PCB design
and layout techniques require a basic understanding of circuit operation.
Although the hand-wired approach results in rapid turn-around at relatively low
production cost, the resulting board is typically not very production worthy, since the
loose wires are easily broken. Also, hand-wired boards may not give the same high-
quality electrical performance that can be achieved using PCBs. When multiple boards
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are required, then the PCB approach is usually the superior solution. PCBs are easily
manufactured in quantity, they are mechanically robust during debug and production,
they provide superior electrical performance, and they provide good consistency (i.e.,
correlation) from one board to another. Correlation between hand-wired DIBs can be
very problematic, since each is electrically unique depending on the exact length and
physical layout of the wires on each board. At very high frequencies, hand-wired boards
are often useless, since they can produce incorrect readings due to their inferior electrical
characteristics. PCBs can be designed, laid out, and fabricated in a matter of a week or
two with the use of computer-aided design (CAD) tools.
To achieve a rapid turn-around with minimal errors, a netlist-based CAD tool for design
and layout should be employed. A netlist is a database describing each interconnection in
the circuit. In addition to the point-to-point interconnection information, the netlist also
includes such information as the footprint, or shape, of each component in the circuit. A
footprint represents the mechanical specification of the component's package.
Information such as pin locations, pad sizes, hole sizes, and package outline shapes to be
printed on the finished PCB are included in the footprint description for each type of
component. Using a netlist-compatible schematic capture tool, the circuit schematic is
drawn on a computer workstation or PC. Then the schematic database (including the
netlist) is used in the board layout process. Once the netlist has been extracted from the
database, laying out the board from a standard template begins. The board template
database represents a head start board design, which includes the shape of the board and
its standard mechanical mounting holes as well as many preplaced standard components,
such as tester connectors. The netlist directs the PCB layout software to import all the
required DlB components from a standard parts library. These components are then
placed and connected as shown in the schematic. The netlist prevents errors in point-to-
point interconnections by refusing to place traces in the layout where they do not belong.
The netlist also guarantees that none of the desired connections are mistakenly omitted.
Once the board layout is completed, each layer of the design is plotted onto transparent
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film for use in PCB fabrication. These plots are commonly known as Gerbers, or Gerber
plots (4).
3.2 PCB Design Workflow
Step 1: Finalize Circuit Design – The Process of PCB design starts with the circuit
design. Circuits can either be hand drawn and later captured electronically, or the circuit
design can be captured directly into a schematic.
Step 2: Choose PCB Design Software – It is important to choose a package that is first
and foremost easy to use, but also capable of completing the PCB design as some
packages won’t be able to handle the complexity. Also, PCB designing to a great extent
needs details of the circuit operation and critically of the components location. Hence,
professional schematic capture software should have the flexibility to set various
constraints for specific nets or groups of components.
Step 3: Capture The Schematic – The circuit design can also be captured electronically
from the start. In general “capturing the schematic” is the process by which each
component is drawn electronically and are interconnected with each other.
Step 4: Design Component Footprints – Once the schematic is complete, the physical
outline of each of the components is drawn. These outlines are what are placed on the
PCB in Copper to allow the components to be soldered to the printed wiring board.
Step 5: Establish PCB Outline – Each project has restrictions related to the board
outline. This should be determined in this step since an idea of component count and area
should be known.
Step 6: Setup Design Rules – With the PCB outline and footprints complete, the
placement should start. Before placement though, the design rules should be setup to
ensure, for example, that components or traces aren’t too close together.
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Step 7: Place Components – Move each component onto the PCB and make all those
components fit together.
Step 8: Manually Route Traces – It’s necessary to manually route critical traces
(clocks, power sensitive analog traces). Once that is complete, the auto router can be
used.
Step 9: Using the Auto Router – There are a handful of rules that will need to be
applied for using an auto router as well, but doing so will save manual trace routing time.
Step 10: Run Design Rule Checker – PCB design software packages have a very good
setup of design rule checkers. It is easy to accidentally violate PCB spacing rules and this
will pinpoint the error saving the designer from having to respin the PCB.
Step 11: Output Gerber Files – Once the board is error free, the gerber files can be
released. A gerber file is a file format used by PCB manufacturing machines to lay out
electrical connections such as traces, vias, and pads (the component footprints on the
PCB). A Gerber file can also contain information for drilling and milling the circuit board
(5).
Figure 3.1 CAD-based PCB design and fabrication process
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3.3 AMC 7891 Daughter Board Design
AMC 7891 needed a custom daughter board to interface to the Mother board which had
all the major resources required to characterize it. The interface is through 4 connectors
on the daughter board which had 40 pins each. Each pin is connected to a corresponding
pin on the mother board which is in turn connected to a resource (supplies, meters,
ground etc.). The resources were thus extended to the custom daughter board and in turn
to the DUT. The DUT is contained in a custom socket with as many pins as the DUT.
Figure 3.2 AMC family mother board
AMC 7891’s 8 channel ADC input pins are connected to supply lines for analog inputs to
the converter. The 4 DAC channels are connected to 4 lines to meter to measure the
output. The 12 GPIO pins are connected to switch between digital input lines and meters
depending on their configuration. The 3 ground pins, 3 power lines, and the 4 pins for
I2C communication are connected to the corresponding lines. Mentor Graphics Design
Capture is used because of the flexibility it offers and also primarily because its library
had all the components needed. Table 3.1 shows the list of net names on AMC 7891
daughter board design.
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Table 3.1 AMC 7891 mother board netlist mapping
Pin # Pin Name Motherboard Net Name Description
1 AVDD DAC2B Supply +/- 20V
2 AGND1 DMM_LO3 Meter ground
3 DGND DGND1 Ground
4 DVDD DAC4_A Supply +/-12.5V
5 IOVDD DAC4_B Supply +/-12.5V
6 SYNC DIG/DRV_IN11 Digital line
7 SCLK SCLK_SCL Clock
8 DIN SDI_SDA SPI/I2C Communication
9 DOUT DIG/DRV_OUT3 Digital line
10 A_OUT4 ANALOG_OUT4 To meter
11 A_OUT3 ANALOG_OUT5 To Meter
12 A_OUT2 ANALOG_OUT11 To Meter
13 A_OUT1 ANALOG_OUT12 To Meter
14 AGND2 DMM_LO3 Meter Ground
15 GPIO-C4 MONITOR4/DAC3A To Meter/Supply
16 GPIO-C3 MONITOR3/DAC3A To Meter/Supply
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Table 3.1 Continued
Pin # Pin Name Motherboard Net Name Description
17 GPIO-C2 MONITOR2/DAC3A To Meter/Supply
18 GPIO-C1 MONITOR1/DAC3A To Meter/Supply
19 DAV DIG/DRV_OUT2 Digital line
20 GPIO-B4 ANALOG_OUT10/DAC2A To Meter/Supply
21 GPIO-B3 ANALOG_OUT9/DAC2A To Meter/Supply
22 GPIO-B2 ANALOG_OUT8/DAC2A To Meter/Supply
23 GPIO-B1 ANALOG_OUT7/DAC2A To Meter/Supply
24 GPIO-A4 ANALOG_OUT6/DAC5B To Meter/Supply
25 GPIO-A3 ANALOG_OUT3/DAC5B To Meter/Supply
26 GPIO-A2 ANALOG_OUT2DAC5B To Meter/Supply
27 GPIO-A1 ANALOG_OUT1/DAC5B To Meter/Supply
28 A_IN1 ADC_DIF2B ADC Diff i/p
29 A_IN2 ADC_DIF2A ADC Diff i/p
30 A_IN3 ADC_DIF1B ADC Diff i/p
31 A_IN4 ADC_DIF1A ADC Diff i/p
32 A_IN5 ADC/DIG3 ADC SE i/p
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Pin # Pin Name Motherboard Net Name Description
33 A_IN6 ADC/DIG2 ADC SE i/p
34 A_IN7 ADC/DIG1 ADC SE i/p
35 A_IN8 ADC/DIG0 ADC SE i/p
36 REF_IN/REF_CMP DAC3B/MONITOR7 Supply+/-20V/To Meter
Figure 3.3 AMC 7891 daughter board schematic capture
3.4 PCB Layout
The connections on the PCB should be identical to the circuit diagram, but while the
circuit diagram is arranged to be readable, the PCB layout is arranged to be functional, so
there is rarely any visible correlation between the circuit diagram and the layout. PCB
layout can be performed manually (using CAD) or in combination with an Auto router.
The best results are usually still achieved using atleast some manual routing - simply
because the engineer has a far better judgment of how to arrange circuitry. The details of
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the circuit operation and critically of components location are very important while
laying out the board. Schematic capture tools allow us to set various constraints for
specific nets or groups of components. Particularly, one can specify minimum line width,
net spacing type, and even maximum and relative signal propagation delays.
3.4.1 Trace Parasitics
One of the most important components on a PCB is the trace. It is easy to think that wires
and traces are not components at all, but are instead represented by the connecting lines
that appear in a schematic. However, PCB traces (and wires in general) are slightly
resistive, slightly inductive, and slightly capacitive in nature. These non ideal circuit
characteristics are known as parasitics. Often, trace parasitics can be ignored, especially
when working with low frequencies and low to moderate current levels. Other times, the
parasitics will have a significant effect on a circuit's behavior. The test engineer should
always be aware of the potential problems that trace parasitics might pose.
The parasitic resistance of a PCB trace is directly proportional to the length of the trace,
and inversely proportional to the height and width of the trace. The equation for
resistance in a uniform conductive material with a rectangular cross section is
R= Ltrace/σWT
where R = trace resistance, Ltrace = trace length, W= trace width, T = trace thickness,
and σ is the conductivity of the trace material.
The inductance of a trace depends on the shape and size of the trace, as well as the
geometry of the signal path through which the currents flow to and from the load
impedance. The inductance of a trace over a ground plane (a configuration known as a
stripline) is dominated by the ratio of the trace-to-ground spacing, D, divided by the trace
width, W. The parasitic inductance of a wide trace routed over a ground or power plane
can be estimated using the equation
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L = µoµrD/W
where L = Inductance per unit length (henrys per meter), µo = magnetic permeability of
free space (400π nH per meter), µr = magnetic permeability of the PCB material divided
by µo, W = trace width, and D = separation between trace and ground plane.
The capacitance between two parallel traces can be estimated using the standard parallel
plate capacitance equation. The parasitic capacitance between two metal plates of area A
is given by the equation
C=εoεrA/D
3.4.2 Grounding
High frequency circuit design requires careful grounding. The “ground” in a circuit is
supposed to be at one potential, but in reality it is not. When ground currents flow
through traces which have non-zero impedance, voltage differences will occur at different
points along the ground path. To minimize these voltages, “ground plane” is used for
control circuit. Most of the signal ground connections are made through vias to this
ground plane rather than through PC traces. For each power supply stage, power ground
and control ground are kept separately.
Figure 3.4 AMC 7891 daughter board ground plane
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3.4.3 Bypass Capacitors
A bypass or decoupling capacitor is a capacitor used to decouple one part of an electrical
network (circuit) from another. Noise caused by other circuit elements is shunted through
the capacitor, reducing the effect they have on the rest of the circuit. The capacitor is used
to bypass the power supply or other high impedance component of a circuit, Hence the
name Bypass Capacitor. A transient load decoupling capacitor and power supply
decoupling bypass capacitor should usually be placed as close as possible to the device
requiring the decoupled signal and the voltage/current respectively. The goal is to
minimize the amount of line inductance and series resistance between the decoupling
capacitor and the supplied device, and the longer the conductor between the capacitor and
the device, the more inductance there is. AMC 7891 daughter board has bypass
capacitors for the input pins of the 8 channel ADC, the 3 power supplies and the external
reference pin.
Figure 3.5 AMC 7891 daughter board layout (layer 4 and all layers visible)
3.5 PCB Materials
Printed circuit boards can be constructed using a variety of materials. The most common
trace material is copper, due to its excellent electrical conductivity. Insulating layers
dielectric are typically laminated together with epoxy resin prepreg. The board is
typically coated with a solder mask that is green in color. The most common insulator
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material is FR4 (fire retardant, type 4) fiberglass. Fiberglass is an inexpensive material
that exhibits good electrical properties up to several hundred megahertz. Thermal
expansion is an important consideration and glass fiber offers the best dimensional
stability. As frequencies approach 1 GHz, more exotic materials such as Teflon or cynate
ester may be needed. Teflon exhibits excellent microwave characteristics including low
signal loss and a low dielectric constant. However, it suffers from poor mechanical
stiffness. Cynate ester is a material with reasonably good high frequency properties and
yet it is stiff enough to withstand the mechanical stress involved in the process of
(production) testing (4).
Figure 3.6 AMC 7891 daughter board (front and back View)
Figure 3.7 AMC 7891 setup
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The progress of very large scale integration (VLS1) technology has brought tremendous
improvement in chip performance as well as gate density. The increasing complexity,
however, renders the testing of a chip much more difficult. For large circuits, manual
testing is quite time consuming and prone to faults. Test time reduction is thus a major
concern in the semiconductor industry today. The remedy is naturally to take into account
automation of characterization and test process. For characterization on bench equipment,
Labview offers a dynamic platform to automate the procedure. More on Labview in
chapter IV.
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Chapter IV
Software Interface – Labview
4.1 Introduction
Labview (short for Laboratory Virtual Instrumentation Engineering Workbench) is a
platform and development environment for a visual programming language from
National Instruments. The purpose of such programming is automating the usage of
processing and measuring equipment in any laboratory setup. Labview ties the creation of
user interfaces (called front panels) into the development cycle. Labview
programs/subroutines are called virtual instruments (VIs). Each VI has three components:
a block diagram, a front panel and a connector panel. The last is used to represent the VI
in the block diagrams of other, calling VIs. Controls and indicators on the front panel
allow an operator to input data into or extract data from a running virtual instrument.
However, the front panel can also serve as a programmatic interface. Thus a virtual
instrument can either be run as a program, with the front panel serving as a user interface,
or, when dropped as a node onto the block diagram, the front panel defines the inputs and
outputs for the given node through the connector pane. This implies each VI can be easily
tested before being embedded as a subroutine into a larger program.
Figure 4.1 Example labview code
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Labview codes can be written just like any other programming language like C. The only
difference is the graphical interface. The example code in figure 4.1 generates a random
number, multiplies it with 10 and displays it continuously, until it is stopped. The
rectangular box is a while loop which executes the code inside it until its “stop” condition
is met, which in this code is done by clicking the stop button. After each iteration, the
while loop waits for 800ms before executing the next one. The number of iterations “i” is
displayed on the front panel using an indicator.
4.2 Advantages
Labview is used in the setup for AMC characterization as well.
Figure 4.2 AMC characterization setup
It offers the benefit of extensive support for accessing instrumentation hardware. The
fully modular character of Labview code allows code reuse without modifications; many
libraries with a large number of functions for data acquisition, signal generation,
mathematics, statistics, signal conditioning, analysis, etc., along with numerous graphical
interface elements make labview a very convenient and desirable tool.
Labview
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4.3 Front Panels
The electrical characteristics of AMC modules are all characterized using labview
interfaces. The complete front panel is built/divided into separate panels for each set of
electrical characteristics. There is a separate front panel for each of the following:
Power switches and power levels
IC communication
IC Registers
Temperature sensors
ADC Linearity
DAC Linearity
Other switches and relays
Thus many electrical characteristics of the functional blocks of all AMCs are
characterized/tested using different combinations of these panels under desirable
conditions by changing the variables on the panels. Power levels are set to the desired
number using controls. Registers are set to default values or are changed on the
register panel based on our desired conditions. “Globals” are used to define variables
that are present in all the three AMCs. (ex.: DAC resolution, ADC resolution, GPIO
count, DAC channel count, ADC channel count). Based on the AMC selected at the
beginning of the test process, these global variables assume values related to that
particular AMC. All in all, the programming method is like that of “if-else” statement
in programming language C.
if(AMC=7824)
............
……….
else if(AMC=7812)
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............
……….
else if(AMC=7891)
............
……….
Labview thus provides huge flexibility to the user to create different working
conditions for the IC under test. As need arises, more functionality can be added to
the same labview program. For example, although initially the labview program was
meant for characterizing AMC 7824, AMC 7812 and AMC 7891 were also made.
Both the new AMCs had GPIOs which were absent in AMC 7824. Hence, initially
there was no VI built for testing the GPIOs. But a separate panel could be added to
the same labview program keeping the already existing functionality intact.
Additional panels thus added are:
GPIO load/short circuit current
DAC load/short circuit current
DAC cross talk
Code versus supply current
Figure 4.3 AMC characterization labview panels
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Figure 4.4 Individual labview panels
4.4 Code Debug
Writing (read: drawing) code for a particular function and making a VI out of it to use it
as a sub-VI in a parent VI is always recommended. A top-down approach while writing
the labview code is always better than putting all the code on one single VI. Nested VIs
make debugging easier. Each VI can be isolated from the other and tested by individually
running it. Thus bad code can easily be quarantined from the good. Also this approach
makes it possible for using Vis individually or as a part of a bigger structure. Individual
VIs can also be borrowed for use in other codes, saving the engineer time and effort it
would take to duplicate them.
Some code for often used functions like data collection and storing in a spreadsheet can
be written as a separate generic VI. This allows for simply dropping in this VI wherever
there is a need for collecting data. Ofcourse the labels and format for the spreadsheet may
differ and can be taken care of with external coding.
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Event driven coding is also a recommended approach. Event cases are triggered by
respective events, say clicking a button. This helps isolate each event and see the results
individually. Also, in case there is error in a particular event, it is easier to debug the code
because of code isolation.
Once the bench setup is ready, the characterization process can begin. More number of
electrical characteristics and parameters can be tested in relatively less time due to
automation using Labview. The electrical characteristics of digital to analog converters of
the AMCs are discussed in chapter V.
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Chapter V
Digital To Analog Converter Characterization
A digital-to-analog converter (DAC or D-to-A) is a device that converts a digital (usually
binary) code to an analog signal (current, voltage, or electric charge). A typical DAC
converts abstract finite precision numbers into a concrete sequence of impulses that are
then processed by a reconstruction filter using some form of interpolation to fill in data
between the impulses. Other DAC methods produce a pulse-density modulated signal that
can then be filtered in a similar way to produce a smoothly varying signal. However,
even with an ideal reconstruction filter, digital sampling introduces quantization error that
makes perfect reconstruction practically impossible. Increasing the digital resolution (i.e.,
increasing the number of bits used in each sample) or introducing sampling dither can
reduce this error. Instead of impulses, usually the sequence of numbers updates the
analog voltage at uniform sampling intervals. These numbers are written to the DAC,
typically with a clock signal that causes each number to be latched in sequence, at which
time the DAC output voltage changes rapidly from the previous value to the value
represented by the currently latched number. The effect of this is that the output voltage
is held in time at the current value until the next input number is latched resulting in a
piecewise constant or 'staircase' shaped output.
Figure 5.1 Piecewise constant output of a conventional practical DAC
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5.1 DAC Architectures
Although the DAC is seen mainly as a black box where digital data goes in and a
representative analog signal comes out, there is much more to it. The digital data can be
either in a serial or parallel data format. Interfaces such as SPI or I2C, which transmit the
digital data stream serially, are like a necklace or chain into the "black box," whereas the
parallel interface loads all necessary bits in one clock cycle into the device. On the other
side of the device, the analog output signal is either a voltage or a current. The different
input interfaces offer variation in the form of the data format and, therefore, in speed, pin
count, chip area, device size, and flexibility. However, both serial and parallel interfaces
will get the digital data into the device. Once the digital data is within the black box, an
input register takes care of operations such as the serial-to-parallel conversion, or in
multi-channel devices stores the data until it is transferred to the individual DAC
registers. The DAC register, which is the connection between the input register and the
DAC architecture, acts like a memory and stores the digital data. In the first days of DAC
design, this DAC register was an external memory block which held the digital data.
Without the DAC register, the output of the DAC would change immediately with any
changes on the external input bus, due to the real-time feeding of the analog circuitry.
The data stays in the DAC register until the user decides to update the DAC register with
new code. The DAC register essentially acts like a flip-flop.
The most common types of electronic DACs are pulse width modulator, over-sampling,
binary weighted, R-2R ladder, string and hybrid DACs, which use a combination of these
techniques in a single converter. There are two principle architectures used in today's
precision DACs, the R2R and string. AMCs use string architecture DACs. Both
architectures are analog circuits with some digital control logic. With a basic R2R
architecture, it is possible to either generate a current output or a voltage output. String
architectures can only generate voltage outputs by using an output buffer. There is no
output buffer implemented in the case of a current output (6).
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5.1.1 String Architecture
The string architecture is as the name implies, a series of resistors placed in series to
build a string. In theory, one would need 256 resistors to build an 8-bit DAC (28 = 256).
Figure 5.2 shows string architecture, including the internal output buffer generating a
voltage output which is equivalent to the digital input code.
Figure 5.2 Principal string architecture with voltage output
Increasing the resolution means also increasing the number of resistors needed to build a
string DAC. For a 16-bit DAC, one would need a total of 65,536 resistors to generate all
the possible voltages/digital steps. However, in the real world of design it is impractical
to implement nearly 66 thousand resistors on a single chip, especially with today's
requirements of small packages, low power dissipation, and low cost. Hence, designers
came up with additional smaller circuitry such as interpolating amplifiers that reduce the
necessary amount of resistors, and tapping points on the resistor string, allowing a more
power-efficient and less space-consuming design. The interpolating amplifier is used as
an output buffer (7).
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5.1.2 String DAC Advantages
Advantages of string DACs are low cost and guaranteed monotonicity. Also important, it
offers low power and small die area, which allow for small packages, making them
desirable in portable applications. Another advantage is that the output buffer is already
included, which eliminates the need for an additional external component on the board.
Secondly, the output buffer isolates internal resistors and analog circuitry from the
outside world. This is quite helpful in low-impedance circuitry. Many applications
require low-glitch energy, which is another benefit of string architecture. However, due
to the higher impedance of the string design, the noise is generally higher than in R2R
architectures.
5.2 DAC Testing
There are a number of parameters that define an IC. These parameters have to meet the
specifications in order for the IC to function desirably. It’s the responsibility of the
characterization engineer to set the specifications right and responsibility of the test
engineer to make sure those are met. There are a number of such defining parameters for
a DAC too. In AMC 7891, the DACs are tested under the following conditions:
AVdd=5 V
Vref=2.5 V
Gain=2
Range=5-0=5 V (unipolar)
Resolution=10 bits
Least Significant Bit (LSB) voltage=5/(2^10)=4.88 mV
Temperature=room(25°C), hot(110°C) and cold(-45°C)
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5.2.1 Offset Error
Offset error, often called 'zero-scale' error, indicates how well the actual transfer function
matches the ideal transfer function at a single point. For an ideal data converter, the first
transition occurs at 0.5 LSB above zero. For a DAC, offset error is the analog output
response to an input code of all zeros.
Figure 5.3 DAC offset error
At room temperature (25°C), the DAC has a maximum offset error of ±10 mV.
5.2.2 Offset Error Drift
Offset-error drift is the variation in offset error due a change in ambient temperature,
typically expressed in ppm/°C. The offset error temperature coefficient is found to be
typically ±1 ppm/°C.
5.2.3 Integral Non-Linearity
Integral nonlinearity (INL) is a term describing the maximum deviation between the ideal
output of a DAC and the actual output level (after offset and gain errors have been
removed). INL is often called 'relative accuracy.' The maximum INL of DAC under all
possible conditions is ±1 LSB.
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Figure 5.4 DAC integral non-linearity
5.2.4 Differential Non-Linearity
For a DAC, DNL error is the difference between the ideal and the measured output
responses for successive DAC codes. An ideal DAC response would have analog output
values exactly one code (LSB) apart (DNL = 0). (A DNL specification of greater than or
equal to 1LSB guarantees monotonicity).
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Figure 5.5 DAC differential non-linearity
Typically the DNL is measured around ±0.3 LSB, but will not exceed a maximum of ±1
LSB under all possible working conditions.
5.2.5 Gain Error
The gain error of a DAC indicates how well the slope of an actual transfer function
matches the slope of the ideal transfer function. Gain error is usually expressed in LSB or
as a percent of full-scale range (%FSR), and it can be calibrated out with hardware or in
software. Gain error is the full-scale error minus the offset error. Typically gain error for
this DAC is around ±0.025 %FSR. Under any condition it will not go beyond ±0.15
%FSR.
Figure 5.6 DAC gain error
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5.2.6 Gain Error Drift
Gain-error drift is the variation in gain error due to a change in ambient temperature,
typically expressed in ppm/°C and it is typically found to be ±1 ppm/°C.
5.2.7 Full Scale Error
Full-scale error equals offset error + gain error, as shown in the figure. At room
temperature and a full scale range of 5V this error is a maximum of ± 10 mV.
Figure 5.7 DAC full scale error
5.2.8 Digital Feedthrough
Digital feedthrough is the noise that appears on a DAC output when the digital control
lines are toggled. In the figure, feedthrough on the DAC output is the result of noise from
the serial clock signal. When /CS is high, digital feedthrough is typically found to be 0.15
nV-S (8).
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Figure 5.8 Digital feedthrough in a DAC
5.2.9 Glitch Impulse
Glitch impulse is the voltage transient that appears at the DAC output when a major-carry
transition occurs. Typically measured as nV•s, it equals the area under the curve on a
voltage-vs-time graph. At the major-carry transition (around mid-scale), either the MSB
changes from low to high and all other bits change from high to low, or the MSB changes
from high to low and all other bits change from low to high. For example, 01111111 to
10000000 is a major-carry transition. Major-carry transitions often produce the worst
switching noise. Here, digital to analog glitch energy is measured when code changes
from 0x7FFh to 0x800h and from 0x800h to 0x7FFh and is found that it is typically
around 0.15 nV-S.
5.2.10 Settling Time
For a DAC, settling time is the interval between a command to update (change) its output
value and the instant it reaches its final value, within a specified percentage. Settling time
is affected by the slew rate of an output amplifier and by the amount of amplifier ringing
and signal overshoot. Output range is set to 0 to 5 V. When code is changed from 0020h
to FD0h, time it takes to reach 0.5LSB is measured under load conditions of RL= 2kΩ
and CL =200 pF, and is found to not exceed 5µs.
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Figure 5.9 DAC settling time measurement (a) referenced to a digital signal; (b)
reference to the DAC output 50% point.
5.2.11 Slew Rate
Slew rate is the maximum rate at which a DAC output can change. For a DAC with
output amplifier, the specified slew rate is typically that of the amplifier. The output
voltage of AMC DAC changes at a maximum rate of 2.2 V/µs.
Figure 5.10 Settling time and glitch energy
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Just like DACs, the ADCs, either independently or along with other functional blocks of
AMC, have to be characterized and tested for their parameters. The same is discussed in
the following chapter.
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Chapter VI
Analog To Digital Converter and GPIO Characterization
An analog-to-digital converter (abbreviated ADC, A/D or A to D) is a device which
converts a continuous quantity to a discrete time digital representation. The digital output
may use different coding schemes. An ADC may also provide an isolated measurement.
It performs the reverse operation of a digital-to-analog converter (DAC).
6.1 ADC Architectures
The most common ways of implementing an electronic ADC are direct conversion or
flash ADC, ramp-compare, Wilkinson, integrating (also dual-slope or multi-slope ADC),
delta-encoded or Counter-ramp, pipeline (also called sub-ranging quantizer), Sigma-Delta
(also known as a Delta-Sigma), Time-interleaved, ADC with intermediate FM stage, and
successive-approximation ADC. The AMC family uses successive-approximation
register or SAR ADCs in their architecture.
6.1.1 Successive-Approximation Register ADC
A SAR ADC uses a comparator to reject ranges of voltages, eventually settling on a final
voltage range. Successive approximation works by constantly comparing the input
voltage to the output of an internal digital to analog converter (DAC, fed by the current
value of the approximation) until the best approximation is achieved. At each step in this
process, a binary value of the approximation is stored in a successive approximation
register (SAR). The SAR uses a reference voltage (which is the largest signal the ADC is
to convert) for comparisons. For example if the input voltage is 60 V and the reference
voltage is 100 V, in the 1st clock cycle, 60 V is compared to 50 V (the reference, divided
by two. This is the voltage at the output of the internal DAC when the input is a '1'
followed by zeros), and the voltage from the comparator is positive (or '1') (because 60 V
is greater than 50 V). At this point the first binary digit (MSB) is set to a '1'. In the 2nd
clock cycle the input voltage is compared to 75 V (being halfway between 100 and 50 V:
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This is the output of the internal DAC when its input is '11' followed by zeros) because
60 V is less than 75 V, the comparator output is now negative (or '0'). The second binary
digit is therefore set to a '0'. In the 3rd clock cycle, the input voltage is compared with
62.5 V (halfway between 50 V and 75 V: This is the output of the internal DAC when its
input is '101' followed by zeros). The output of the comparator is negative or '0' (because
60 V is less than 62.5 V) so the third binary digit is set to a 0. The fourth clock cycle
similarly results in the fourth digit being a '1' (60 V is greater than 56.25 V, the DAC
output for '1001' followed by zeros). The result of this would be in the binary form 1001.
This is also called bit-weighting conversion, and is similar to a binary search. Because the
approximations are successive (not simultaneous), the conversion takes one clock-cycle
for each bit of resolution desired. The clock frequency must be equal to the sampling
frequency multiplied by the number of bits of resolution desired. For example, to sample
audio at 44.1 kHz with 32 bit resolution, a clock frequency of over 1.4 MHz would be
required. ADCs of this type have good resolutions and quite wide ranges. They are more
complex than some other designs (9).
Figure 6.1 Successive Approximation ADC Block Diagram
6.2 ADC Testing
In AMC 7891, the ADCs are tested under the following conditions:
AVdd=5 V
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Vref=2.5 V
Gain=2
Code Range=0 to 1023
Resolution=10 bits
Least Significant Bit (LSB) voltage=5/(2^10)=4.88 mV
Temperature=room(25°C), hot(110°C) and cold(-45°C)
6.2.1 Offset Error
Offset error, often called 'zero-scale' error, indicates how well the actual transfer function
matches the ideal transfer function at a single point. For an ideal data converter, the first
transition occurs at 0.5LSB above zero. In an ideal A/D converter, an input voltage of
quanta / 2 will just barely cause an output code transition from zero to a count of one.
Any deviation from this is called Zero Scale Error, Zero Scale Offset Error, or Offset
Error. This error is positive or negative when the first transition point is higher or lower
than ideal, respectively. Offset error is a constant and can easily be factored or calibrated
out. Offset error may be expressed in percent of full scale voltage, Volts or in LSB. AMC
7891 ADC typically has offset error of ±1 LSB and offset error match of ±0.4 LSB.
Figure 6.2 ADC offset error
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6.2.2 Integral Non-Linearity
INL describes the bow in the transfer function. INL is the maximum deviation of the
transfer function from a straight line between two points along the input-output transfer
curve. The maximum INL of ADC under all possible conditions is ±1 LSB, but typically
its around ±0.5 LSB.
INL = | [(VD - VZERO)/VLSB-IDEAL] - D | , where 0 < D < 2N-1.
Figure 6.3 ADC integral non-linearity
6.2.3 Differential Non-Linearity
DNL is the difference between the ideal and the actual input code width. The input code
width is the range of input values that produces the same digital output code. For an
ADC, the analog-input levels that trigger any two successive output codes should differ
by one LSB (DNL
= 0). Any deviation from one LSB is defined as DNL. For positive DNL we look at the
widest input code range. For negative DNL we look at the narrowest code range.
Typically the DNL is measured around ±0.5 LSB, but will not exceed a maximum of ±1
LSB under all possible working conditions.
DNL = |[(VD+1- VD)/VLSB-IDEAL - 1] | , where 0 < D < 2N
- 2.
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Figure 6.4 ADC differential non-linearity
6.2.4 Gain Error
Gain Error, or Full-Scale Gain Error, is a deviation from the ideal slope of the transfer
function. It is the same as full-scale error with the offset error subtracted. If we shift the
actual transfer curve so that zero scale offset error becomes zero, the difference between
the actual and ideal transitions to full scale is the Gain Error. Typically gain error for this
ADC is around ±0.5 LSB and gain error match between the channels is typically ±0.4
LSB. Gain matching indicates how well the gains of all channels in a multichannel ADC
are matched to each other. To calculate gain matching, apply the same input signal to all
channels, and report the maximum deviation in gain (8).
Figure 6.5 ADC gain error
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6.3 General Purpose Input/Output
GPIO is a generic pin on a chip whose behavior (including whether it is an input or
output pin) can be controlled (programmed) through software. GPIO pins have no special
purposes on themselves, and go unused by default. The idea is that sometimes the system
integrator building a full system that uses the chip might find useful to have a handful of
additional digital control lines, and having these available from the chip can save the
hassle of having to arrange additional circuitry to provide them. GPIO lines can thus
provide additional control and monitoring when the microcontroller or chipset has
insufficient I/O ports, or in systems where serial communication and control from a
remote location is advantageous.
GPIO capabilities include:
direction: GPIO pins can be configured to be input or output
enable mask (aka GPIO mask): GPIO pins can be enabled/disabled
input values are readable (typically high=1, low=0)
output values are writable/readable
GPIO peripherals vary quite widely. In some cases, they are very simple, a group of pins
that can be switched as a group to either input or output. In others, each pin can be set up
flexibly to accept or source different logic voltages, with configurable drive strengths and
pull up/downs. The input and output voltages are typically limited to the supply voltage
of the device with the GPIOs on, and may be damaged by greater voltages.
AMC 7891 has 12 GPIOs powered by DVdd supply of the chip. Vih,Vil and Voh, Vol
are the characteristics mentioned in the specification sheet for these digital GPIO lines.
They are defined as follows:
Vih : The minimum voltage applied to the input which will be accepted by the device as
logic high.
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Vil : The maximum voltage applied to the input which will be accepted by the device as
logic low.
Voh : The minimum voltage level for logic high, at the output of the gate, under load.
Vol : The maximum voltage level for logic low, at the output of the gate, under load.
6.4 GPIO Results
Table 6.1 shows the measurements that are recorded after testing various chips:
Table 6.1 GPIO results
DVdd (volts) Min (v) Max
(v)
Vih
1.8 0.7*DVdd
3.3 2.1
5.5 2.1
Vil
1.8 0.3
3.3 0.8
5.5 0.8
Voh
1.8, Sourcing 1.6mA DVdd-0.2
3.3, Sourcing 1.6mA DVdd-0.2
5.5, Sourcing 1.6mA DVdd-0.2
Vol
1.8, Sinking 1.6mA 0.4
3.3, Sinking 1.6mA 0.4
5.5, Sinking 1.6mA 0.4
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Chapter VII
Conclusion and Future Work
7.1 Conclusion
The test solution described combines both hardware and software to test SOCs like
Analog Monitoring and Control family of chips, showing the design process flow with all
the steps followed. By using a modular approach, the solution becomes generic, such that
it can be employed in testing many generations of AMCs with very few changes in the
software, and a series of daughter boards with no changes in the mother board, hence
saving time and revenue. The test solution developed produces results as expected and as
well provides an expandable platform to accommodate future testing of AMCs. Multiple
testing and statistical analysis confirms the repeatability and accuracy of the test solution,
leading to the characterization of the device and determination of the datasheet limits for
the new device. The aim of capturing markets is partially fulfilled by shipping the
samples to the respective customers within the specified deadlines. Full characterization
of the parts continues, bench to ATE correlation and qualification test are performed
before releasing the product to the markets.
7.2 Future Work
The skeletal framework for testing any type of AMC has now been developed, and
implementing this system for other devices is as easy as developing new daughter boards
with change only in the socket footprints and mapping to the motherboard. Since the
motherboard has all the test circuitry required, daughterboard can be fitted on it and the
design will then be complete. The software can be made compatible with the new
products with minimal changes to it. As far as the software is concerned, there is hardly
any limitation to the functionality that could be tested using this setup. The only limiting
factor could be the resources available on the hardware front: the motherboard.
Nevertheless there is still some room for future products with some excess resources
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already available anticipating future growth. The setup can be used not only for future
AMCs but for other types of ICs as well, like independent DACs and ADCs for example.
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