6.776 high speed communication circuits lecture …...advantages-pmos gate no longer loads the...
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6.776High Speed Communication Circuits
Lecture 7High Freqeuncy, Broadband Amplifiers
Massachusetts Institute of TechnologyFebruary 24, 2005
Copyright © 2005 by Hae-Seung Lee and Michael H. Perrott
H.-S. Lee & M.H. Perrott MIT OCW
High Frequency, Broadband Amplifiers
The first thing that you typically do to the input signal is amplify it
Function- Boosts signal levels to acceptable values- Provides reverse isolation
Key performance parameters- Gain, bandwidth, noise, linearity
VLC1 RL
L1Delay = xCharacteristic Impedance = Zo
Transmission Line
Z1
VinC2
dieAdjoining pinsConnector
Controlled ImpedancePCB trace
package
On-ChipDrivingSource
AmpVout
H.-S. Lee & M.H. Perrott MIT OCW
Gain-bandwidth Trade-off
Common-source amplifier example
Vdd
RL
Ctot
vo
Ctot: total capacitance at output node
vin
+-
+-
DC gainVbias
3 dBbandwidth
Gain-bandwidth
H.-S. Lee & M.H. Perrott MIT OCW
Gain-bandwidth Trade-off
Common-source amplifier example
RL=RL1
RL=RL3
RL=RL3
Given the ‘origin pole’ gm/Ctot, higher bandwidth is achieved only at the expense of gainThe origin pole gm/Ctot must be improved for better GB
H.-S. Lee & M.H. Perrott MIT OCW
Gain-bandwidth Improvement
How do we improve gm/Ctot?Assume that amplifier is loaded by an identical amplifier and fixed wiring capacitance is negligibleSince and
To achieve maximum GB in a given technology, use minimum gate length, bias the transistor at maximum
When velocity saturation is reached, higher does not give higher gmIn case fixed wiring capacitance is large, power consumption must be also considered
H.-S. Lee & M.H. Perrott MIT OCW
Gain-bandwidth Observations
Constant gain-bandwidth is simply the result of single-pole role off – it’s not fundamental!It implies a single-pole frequency response may not be the best for obtaining gain and bandwidth simultaneouslySingle-pole role off is necessary for some circuits, e.g. for stability, but not for broad-band amplifiers
H.-S. Lee & M.H. Perrott MIT OCW
Assumptions (for now) for Bandwidth Analysis
Assume for now that amplifier is loaded by an identical amplifier and by fixed wiring capacitanceAssume amplifier is driven by an ideal voltage source for now
Intrinsic performance- Defined as the bandwidth achieved for a given gain when Cfixed
is negligible- Amplifier approaches intrinsic performance as its device sizes
(and current) are increasedIn practice, point of diminishing return for bandwidth vs. size (and power) of amplifier is roughly where Cin+Cout = Cfixed
Amp Amp
Cfixed
CinCin
Ctot = Cout+Cin+Cfixed
Cout
H.-S. Lee & M.H. Perrott MIT OCW
The Miller Effect
Concerns impedances that connect from input to output of an amplifier
Input impedance:
Output impedance:
Amp
Zin
Zf
Av
ZL
VoutVin
Zout
H.-S. Lee & M.H. Perrott MIT OCW
Example: Miller Capacitance
Consider Cgd in the MOS device as Cf- Assume gain is negative
Input capacitance:
Looks like much larger capacitance by |Av|
Amp
Zin
Av
ZL
VoutVin
Zout
Cf
H.-S. Lee & M.H. Perrott MIT OCW
Example: Miller Capacitance
Output impedance:
This makes sense because the input of the amplifier is ‘virtual ground’ if gain is large
Amp
Zin
Av
ZL
VoutVin
Zout
Cf
H.-S. Lee & M.H. Perrott MIT OCW
Amplifier Example – CMOS Inverter
The Miller effect gives a quick way to estimate the bandwidth of an amplifer without solving node equations: intuition!Assume that we set Vbias the amplifier nominal output is such that NMOS and PMOS transistors are all in saturation- Note: this topology VERY sensitive to Vbias : some feedback
biasing would be required (6.301)
Cfixed
Ctot = Cdb1+Cdb2 + Cgs3+Cgs4 + K(Cov3+Cov4) + Cfixed
M2
M1
M4
M3
Miller multiplication factor
Vbias
vin
(+Cov1+Cov2)
vout
H.-S. Lee & M.H. Perrott MIT OCW
Transfer Function of CMOS Inverter
Low Bandwidth!
Cfixed
Ctot = Cdb1+Cdb2 + Cgs3+Cgs4 + K(Cov3+Cov4) + Cfixed
M2
M1
M4
M3
Miller multiplication factor
Vbias
vin
(+Cov1+Cov2)
vout
1
voutvin
f
slope = -20 dB/dec
(gm1+gm2)(ro1||ro2)
2πCtot(ro1||ro2)1 gm1+gm2
2πCtot
H.-S. Lee & M.H. Perrott MIT OCW
Add Resistive Feedback?
Bandwidth extended and less sensitivityto bias offset(does not improve GB, though)
Cfixed
Ctot = Cdb1+Cdb2 + Cgs3+Cgs4 + K(Cov3+Cov4) + CRf /2 + Cfixed
M2
M1
M4
M3
Miller multiplication factor
Vbias
vin
(+Cov1+Cov2)
voutRf
1
voutvin
f
slope = -20 dB/dec
(gm1+gm2)(ro1||ro2)
2πCtot(ro1||ro2)1 gm1+gm2
2πCtot
(gm1+gm2)Rf
2πCtotRf
1
H.-S. Lee & M.H. Perrott MIT OCW
We Can Still Do Better
We are fundamentally looking for high gm to capacitance ratio to get the highest bandwidth- PMOS degrades this ratio- Gate bias voltage is constrainedHowever, when Cfixed is dominant and power consumption is important, the PMOS increases gm without additional powerOn the other hand, below velocity saturation, higher gm can be achieved by biasing the gate of M1 close to Vdd instead of using PMOS
Cfixed
Ctot = Cdb1+Cdb2 + Cgs3+Cgs4 + K(Cov3+Cov4) + CRf /2 + Cfixed
M2
M1
M4
M3
Miller multiplication factor
Vbias
vin
(+Cov1+Cov2)
voutRf
H.-S. Lee & M.H. Perrott MIT OCW
Take PMOS Out of the Signal Path
CL
M2
M1
Vbias
vin
voutRf
Vbias2Ibias
CLM1
Vbias
vin
voutRf
Advantages- PMOS gate no longer loads the signal- NMOS device can be biased at a higher voltage (higher gm up
to velocity sat. limit)
Issue- PMOS is not an efficient current provider (Id/drain cap Cgd+Cdb)
Drain cap close in value to Cgs- Signal path is loaded by cap of Rf and drain cap of PMOS
H.-S. Lee & M.H. Perrott MIT OCW
Shunt-Series Amplifier
Ibias
M1
Vbias
vin
voutRf
R1
Rs
RL
Rin Rout
M1
Vbias
vinvout
Rf
R1
Rs
RL
Rin Rout
Use resistors to control the bias, gain, and input/output impedances- Improves accuracy over process and temp variations
Issues- Degeneration of M1 lowers slew rate for large signal
applications (such as limit amps)- There are better high speed approaches – the advantage
of this one is simply accuracy
H.-S. Lee & M.H. Perrott MIT OCW
Shunt-Series Amplifier – Analysis Snapshot
From Chapter 9 (8) of Tom Lee’s book:- Gain
- Input resistance
- Output resistance
M1
Vbias
vinvout
Rf
R1
Rs
RL
Rin Rout
vx
Same for Rs = RL!
H.-S. Lee & M.H. Perrott MIT OCW
NMOS Load Amplifier
CfixedM1Vbias
vin
vout
M2
gm2
1
1
voutvin
f
slope = -20 dB/dec
gm12πCtot
gm1
2πCtot
gm2
gm2Ctot = Cdb1+Csb2+Cgs2 + Cgs3+KCov3 + Cfixed
Miller multiplication factor(+Cov1)
M3
Vdd
Id
Gain set by the relative sizing of M1 and M2
H.-S. Lee & M.H. Perrott MIT OCW
Design of NMOS Load Amplifier
CfixedM1Vbias
vin
vout
M2
gm2
1
Ctot = Cdb1+Csb2+Cgs2 + Cgs3+KCov3 + Cfixed
Miller multiplication factor(+Cov1)
M3
Vdd
Id
Size transistors for gain and speed- Choose minimum L for maximum speed- Choose ratio of W1 to W2 to achieve appropriate gain
H.-S. Lee & M.H. Perrott MIT OCW
Advantage/Disadvantages of NMOS Load Amplifier
Gain is well controlled despite process variations
NMOS is not a low parasitic load- Cgs of M2 loads the output
Biasing Problem: VT of M2 lowers the gate bias voltage of the next stage (thus lowering its achievable ft)- Severely hampers performance when amplifier is cascaded- One paper addressed this issue by increasing Vdd of NMOS
load (see Sackinger et. al., “A 3-GHz 32-dB CMOS Limiting Amplifier for SONET OC-48 receivers”, JSSC, Dec 2000)
H.-S. Lee & M.H. Perrott MIT OCW
Resistor Loaded Amplifier (Unsilicided Poly)
M1
RL
vout
M2
Cfixed
Id
Vbias
vin
Ctot = Cdb1+CRL/2 + Cgs2+KCov2 + Cfixed
Miller multiplication factor(+Cov1)
1
voutvin
f
slope = -20 dB/dec
gm12πCtot
gm1RL
2πRLCtot
1
Vdd
This is the fastest non-enhanced amplifier topology- Unsilicided poly is a low parasitic load (i..e, has a good
current to capacitance ratio)- Output can go near VddAllows following stage to achieve high ft , but at the cost of gain (max gain ∝ VRL
)
- Linear settling behavior (in contrast to NMOS load)
H.-S. Lee & M.H. Perrott MIT OCW
Gain Limitations in Resistor Loaded Amplifier
Want high for high bandwidth, but this reduces gain. With low Vdd gain is very limited.
H.-S. Lee & M.H. Perrott MIT OCW
Implementation of Resistor Loaded Amplifier
Typically implement using differential pairs
Benefits- Bias stability without feedback- Common-mode rejection
Negative- More power than single-ended version
M6
M1 M2
M5
αIbias
Vin+
R1
Vin-
R2Vo+
Vo-
M7
M3 M4
Cfixed Cfixed
Ibias
Ibias/2
Vdd
H.-S. Lee & M.H. Perrott MIT OCW
Open-Circuit Time Constants
The Miller capacitance analysis is a reasonably good method, but is somewhat limited in applicable topologiesthe OCT method is more general and often gives more insightsSystematic, intuitive method to determine bandwidth of amplifiersOften gives fairly accurate estimates of bandwidth if there is a dominant polePoints to the bandwidth bottleneck: this is the real value of the OCT method!Limitation: fails in RF circuits with zero enhancements or inductorsIn typical broadband amplifiers, the OCT estimate is too pessimistic due to multiple poles at around similar frequencies
H.-S. Lee & M.H. Perrott MIT OCW
Open Circuit Time Constant Method
Assumptions: No zero near or ωhZero well below wh is handled by treating corresponding capacitor as sort circuitNegative real poles only (complex conjugate poles with low Q reduces accuracy of estimation only moderately)No inductors
( )( ) ( )
( ) nnn
ni
o
ssa
sssa
VVsA
ττττττ
τττ
⋅⋅⋅⋅⋅⋅+⋅⋅⋅+++=
+⋅⋅⋅++==
2121
0
21
0
1
111)(
If we ignore the higher order terms
∑=
=+⋅⋅⋅++
≈= n
iin
hh f1
1
21
12ττττ
πω
H.-S. Lee & M.H. Perrott MIT OCW
OCT Method, Continued
It can be shown
∑=
==
≈
∑=∑
n
jjo
h
n
jjo
n
ii
1
1
11
τω
ττ
Thus
:open-circuit time constantsjjojo CR=τwhere
The open-circuit time constants can be found without node equations, often by inspection
H.-S. Lee & M.H. Perrott MIT OCW
OCR Calculation
Let’s consider an arbitrary circuit with resistors, dependent sources, and n capacitors (no inductors!). Redraw the circuit to pull capacitors out around the perimeter.
C1+-
C2
+-R1o
R2o
RnoCn
H.-S. Lee & M.H. Perrott MIT OCW
OCT’s for CS Amplifier
CL
vo
RL
Cgs
Cgd
R1o
R2o
R3oRS
By inspection:
It takes some work to figure
H.-S. Lee & M.H. Perrott MIT OCW
OCT’s for CS Amplifier
RL
vgsRS
+
-
gmvgs
vt
it+
-
vo
H.-S. Lee & M.H. Perrott MIT OCW
OCT’s for CS Amplifier
If RS=0, then τ1o=0,τ2o=CgdRL, and τ3o=CLRL so RLdetermines the bandwidthHaving individual OCT values identifies the bandwidth bottleneck and suggests a game planNote:for cascased amplifiers, CL does not include Miller cap of the next stage. Instead, τ2o corresponding to the next stage Miller cap is separately calculated
H.-S. Lee & M.H. Perrott MIT OCW
Cascode to Improve Bandwidth
Lmv Rga 1−=Midband gain: by inspectionVCC
RL
vo
vi
RS M1
M2
22,2,
11mbmeffm
effL gggR
+==
1, oeffS rR =
So RR =1
( )
22
1
,1
,,112
1
1
1
mbm
SmS
effLSmS
S
effLeffLmoo
ggRgR
RRgRR
RRgRR
++
+=
++=
⎟⎟⎠
⎞⎜⎜⎝
⎛++=
22,2,3
11
mbmeffmeffSo ggg
RR+
≈≈
LL
effSeffm
Lbo RR
Rg
RrR ≈+⎟⎟⎟⎟
⎠
⎞
⎜⎜⎜⎜
⎝
⎛
++=
,,
4 11
H.-S. Lee & M.H. Perrott MIT OCW
Cascode
Improves bandwidth in a single-stage amplifier
Problem in cascading: - Bias point: Reduces ωt of the next stage. PMOS SF is a
possibility but low gm/C ratio is a drawback.